Digital broadcasting system and method of processing data

ABSTRACT

A digital broadcast receiving system includes a known data detector, a carrier recovery unit, and a timing recovery unit. The known data detector may detect known data information inserted and transmitted from a digital broadcast transmitting system and using the known data information to estimate initial frequency offset. The carrier recovery unit may obtain initial synchronization by using the initial frequency offset, and may detect frequency offset from the received data by using the known sequence position indicator so as to perform carrier recovery. The timing recovery unit may detect timing error information from the received signal by using the known sequence position indicator so as to perform timing recovery.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.13/418,297, filed on Mar. 12, 2012, now U.S. Pat. No. 8,488,717, whichis a continuation of U.S. patent application Ser. No. 13/198,643, filedon Aug. 4, 2011, now U.S. Pat. No. 8,218,675, which is a continuation ofU.S. patent application Ser. No. 12/965,754, filed on Dec. 10, 2010, nowU.S. Pat. No. 8,023,047, which is a continuation of U.S. patentapplication Ser. No. 11/774,538, filed on Jul. 6, 2007, now U.S. Pat.No. 7,881,408, which claims the benefit of earlier filing date and rightof priority to Korean Patent Application No. 10-2007-0029485, filed onMar. 26, 2007, and also claims the benefit of U.S. ProvisionalApplication No. 60/908,630, filed on Mar. 28, 2007, the contents ofwhich are all hereby incorporated by reference herein in their entirety.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to a digital broadcasting system andmethod of processing data.

2. Discussion of the Related Art

The Vestigial Sideband (VSB) transmission mode, which is adopted as thestandard for digital broadcasting in North America and the Republic ofKorea, is a system using a single carrier method. Therefore, thereceiving performance of the digital broadcast receiving system may bedeteriorated in a poor channel environment. Particularly, sinceresistance to changes in channels and noise is more highly required whenusing portable and/or mobile broadcast receivers, the receivingperformance may be even more deteriorated when transmitting mobileservice data by the VSB transmission mode.

SUMMARY OF THE INVENTION

Accordingly, the present invention is directed to a digital broadcastingsystem and a method of processing data that substantially obviate one ormore problems due to limitations and disadvantages of the related art.

An object of the present invention is to provide a digital broadcastingsystem and a method of processing data that are highly resistant tochannel changes and noise.

Another object of the present invention is to provide a digitalbroadcasting system and a method of processing data that can enhance thereceiving performance of a digital broadcast receiving system byperforming additional encoding on mobile service data and bytransmitting the processed data to the receiving system.

A further object of the present invention is to provide a digitalbroadcasting system and a method of processing data that can alsoenhance the receiving performance of a digital broadcast receivingsystem by inserting known data already known in accordance with apre-agreement between the receiving system and the transmitting systemin a predetermined area within a data area.

Additional advantages, objects, and features of the invention will beset forth in part in the description which follows and in part willbecome apparent to those having ordinary skill in the art uponexamination of the following or may be learned from practice of theinvention. The objectives and other advantages of the invention may berealized and attained by the structure particularly pointed out in thewritten description and claims hereof as well as the appended drawings.

To achieve these objects and other advantages and in accordance with thepurpose of the invention, as embodied and broadly described herein, adigital broadcast transmitting system includes a service multiplexer anda transmitter. The service multiplexer multiplexes mobile service dataand main service data at pre-determined data rates and, then, transmitsthe multiplexed service data to the transmitter. The transmitterperforms additional encoding on the mobile service data transmitted fromthe service multiplexer and, also, groups a plurality of mobile servicedata packets having encoding performed thereon so as to configure a datagroup.

Herein, the transmitter may multiplex a mobile service data packetincluding the mobile service data and a main service data packetincluding the main service data in packet units and may transmit themultiplexed data packets to a digital broadcast receiving system.Herein, the transmitter may multiplex the data group and the mainservice data packet in a burst structure, wherein the burst section maybe divided in a burst-on section including the data group, and aburst-off section that does not include the data group. The data groupmay be divided into a plurality of regions based upon a degree ofinterference of the main service data. A long known data sequence may beperiodically inserted in the region having no interference with the mainservice data.

In another aspect of the present invention, a digital broadcastreceiving system may use the known data sequence for demodulating andchannel equalizing processes. When receiving only the mobile servicedata, the digital broadcast receiving system turns power on only duringthe burst-on section so as to process the mobile service data. Herein,by detecting the position of the known data being transmitted from thetransmitting system, the initial frequency offset may be compensated.The receiving system may use the detected known data (or sequence)position indicator in carrier recovery, timing recovery, and phasecompensation processes.

It is to be understood that both the foregoing general description andthe following detailed description of the present invention areexemplary and explanatory and are intended to provide furtherexplanation of the invention as claimed.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings, which are included to provide a furtherunderstanding of the invention and are incorporated in and constitute apart of this application, illustrate embodiment(s) of the invention andtogether with the description serve to explain the principle of theinvention. In the drawings:

FIG. 1 illustrates a block diagram of a digital broadcast systemaccording to an embodiment of the present invention;

FIG. 2 illustrates a block diagram of a service multiplexer of FIG. 1according to an embodiment of the present invention;

FIG. 3 illustrates a block diagram of a transmitter of FIG. 1 accordingto an embodiment of the present invention;

FIG. 4 illustrates a block diagram of a pre-processor of FIG. 3according to an embodiment of the present invention;

FIG. 5( a) to FIG. 5( e) illustrate process steps of error correctionencoding and error detection encoding processes according to anembodiment of the present invention;

FIG. 6A and FIG. 6B respectively illustrate examples of a data structurebefore and after a data deinterleaver in a digital broadcasttransmitting system according to the present invention;

FIG. 7 illustrates an example of a process for dividing a RS frame inorder to configure a data group according to the present invention;

FIG. 8 illustrates an example of an operation of a packet multiplexerfor transmitting the data group according to the present invention;

FIG. 9 illustrates a block diagram of a block processor according to anembodiment of the present invention;

FIG. 10 illustrates a detailed block diagram of a symbol encoder of FIG.9;

FIG. 11( a) to FIG. 11( c) illustrates an example of a variable lengthinterleaving process of a symbol interleaver shown in FIG. 9;

FIG. 12A and FIG. 12B respectively illustrate block diagrams of a blockprocessor according to another embodiment of the present invention;

FIG. 13( a) to FIG. 13( c) illustrates an example of a block encodingand trellis encoding processes according to the present invention;

FIG. 14 illustrates a block diagram of a trellis encoding moduleaccording to an embodiment of the present invention;

FIG. 15A and FIG. 15B illustrate a block processor and a trellisencoding module being connected to one another according to the presentinvention;

FIG. 16 illustrates a block processor according to yet anotherembodiment of the present invention;

FIG. 17 illustrates a block processor according to yet anotherembodiment of the present invention;

FIG. 18 illustrates an example of a group formatter inserting andtransmitting a transmission parameter;

FIG. 19 illustrates an example of a block processor inserting andtransmitting a transmission parameter;

FIG. 20 illustrates an example of a packet formatter inserting andtransmitting a transmission parameter;

FIG. 21 illustrates an example for inserting and transmitting thetransmission parameter in a field synchronization segment area;

FIG. 22 illustrates a block diagram of a digital broadcast receivingsystem according to the present invention;

FIG. 23 illustrates a data structure showing an example of known databeing periodically inserted in valid data according to the presentinvention;

FIG. 24 illustrates a block diagram showing a structure of a demodulatorof a digital broadcast receiving system shown in FIG. 22;

FIG. 25 illustrates a detailed block diagram of the demodulator of thedigital broadcast receiving system shown in FIG. 22;

FIG. 26 illustrates a block diagram of a frequency offset estimatoraccording to an embodiment of the present invention;

FIG. 27 illustrates a block diagram of a known data detector and initialfrequency offset estimator according to the present invention;

FIG. 28 illustrates a block diagram of a partial correlator shown inFIG. 27;

FIG. 29 illustrates a block diagram of a DC remover according to anembodiment of the present invention;

FIG. 30 illustrates an example of shifting sample data inputted to a DCestimator shown in FIG. 29;

FIG. 31 illustrates a block diagram of a DC remover according to anotherembodiment of the present invention; and

FIG. 32 illustrates an example of an error correction decoding processaccording to the present invention.

DETAILED DESCRIPTION OF THE INVENTION

Reference will now be made in detail to the preferred embodiments of thepresent invention, examples of which are illustrated in the accompanyingdrawings. Wherever possible, the same reference numbers will be usedthroughout the drawings to refer to the same or like parts. In addition,although the terms used in the present invention are selected fromgenerally known and used terms, some of the terms mentioned in thedescription of the present invention have been selected by the applicantat his or her discretion, the detailed meanings of which are describedin relevant parts of the description herein. Furthermore, it is requiredthat the present invention is understood, not simply by the actual termsused but by the meaning of each term lying within.

Among the terms used in the description of the present invention, mainservice data correspond to data that can be received by a fixedreceiving system and may include audio/video (A/V) data. Morespecifically, the main service data may include NV data of highdefinition (HD) or standard definition (SD) levels and may also includediverse data types required for data broadcasting. Also, the known datacorrespond to data pre-known in accordance with a pre-arranged agreementbetween the receiving system and the transmitting system. Additionally,in the present invention, mobile service data may include at least oneof mobile service data, pedestrian service data, and handheld servicedata, and are collectively referred to as mobile service data forsimplicity. Herein, the mobile service data not only correspond tomobile/pedestrian/handheld service data (M/P/H service data) but mayalso include any type of service data with mobile or portablecharacteristics. Therefore, the mobile service data according to thepresent invention are not limited only to the M/P/H service data.

The above-described mobile service data may correspond to data havinginformation, such as program execution files, stock information, and soon, and may also correspond to NV data. Most particularly, the mobileservice data may correspond to NV data having lower resolution and lowerdata rate as compared to the main service data. For example, if an NVcodec that is used for a conventional main service corresponds to aMPEG-2 codec, a MPEG-4 advanced video coding (AVC) or scalable videocoding (SVC) having better image compression efficiency may be used asthe NV codec for the mobile service. Furthermore, any type of data maybe transmitted as the mobile service data. For example, transportprotocol expert group (TPEG) data for broadcasting real-timetransportation information may be serviced as the main service data.

Also, a data service using the mobile service data may include weatherforecast services, traffic information services, stock informationservices, viewer participation quiz programs, real-time polls & surveys,interactive education broadcast programs, gaming services, servicesproviding information on synopsis, character, background music, andfilming sites of soap operas or series, services providing informationon past match scores and player profiles and achievements, and servicesproviding information on product information and programs classified byservice, medium, time, and theme enabling purchase orders to beprocessed. Herein, the present invention is not limited only to theservices mentioned above. In the present invention, the transmittingsystem provides backward compatibility in the main service data so as tobe received by the conventional receiving system. Herein, the mainservice data and the mobile service data are multiplexed to the samephysical channel and then transmitted.

The transmitting system according to the present invention performsadditional encoding on the mobile service data and inserts the dataalready known by the receiving system and transmitting system (i.e.,known data), thereby transmitting the processed data. Therefore, whenusing the transmitting system according to the present invention, thereceiving system may receive the mobile service data during a mobilestate and may also receive the mobile service data with stabilitydespite various distortion and noise occurring within the channel.

General Description of a Transmitting System

FIG. 1 illustrates a block diagram showing a general structure of adigital broadcast transmitting system according to an embodiment of thepresent invention. Herein, the digital broadcast transmitting includes aservice multiplexer 100 and a transmitter 200. Herein, the servicemultiplexer 100 is located in the studio of each broadcast station, andthe transmitter 200 is located in a site placed at a predetermineddistance from the studio. The transmitter 200 may be located in aplurality of different locations. Also, for example, the plurality oftransmitters may share the same frequency. And, in this case, theplurality of transmitters receives the same signal. Accordingly, in thereceiving system, a channel equalizer may compensate signal distortion,which is caused by a reflected wave, so as to recover the originalsignal. In another example, the plurality of transmitters may havedifferent frequencies with respect to the same channel.

A variety of methods may be used for data communication each of thetransmitters, which are located in remote positions, and the servicemultiplexer. For example, an interface standard such as a synchronousserial interface for transport of MPEG-2 data (SMPTE-310M). In theSMPTE-310M interface standard, a constant data rate is decided as anoutput data rate of the service multiplexer. For example, in case of the8VSB mode, the output data rate is 19.39 Mbps, and, in case of the 16VSBmode, the output data rate is 38.78 Mbps. Furthermore, in theconventional 8VSB mode transmitting system, a transport stream (TS)packet having a data rate of approximately 19.39 Mbps may be transmittedthrough a single physical channel. Also, in the transmitting systemaccording to the present invention provided with backward compatibilitywith the conventional transmitting system, additional encoding isperformed on the mobile service data. Thereafter, the additionallyencoded mobile service data are multiplexed with the main service datato a TS packet form, which is then transmitted. At this point, the datarate of the multiplexed TS packet is approximately 19.39 Mbps.

At this point, the service multiplexer 100 receives at least one type ofmobile service data and program specific information (PSI)/program andsystem information protocol (PSIP) table data for each mobile serviceand encapsulates the received data to each transport stream (TS) packet.Also, the service multiplexer 100 receives at least one type of mainservice data and PSI/PSIP table data for each main service so as toencapsulate the received data to a TS packet. Subsequently, the TSpackets are multiplexed according to a predetermined multiplexing ruleand outputs the multiplexed packets to the transmitter 200.

Service Multiplexer

FIG. 2 illustrates a block diagram showing an example of the servicemultiplexer. The service multiplexer includes a controller 110 forcontrolling the overall operations of the service multiplexer, aPSI/PSIP generator 120 for the main service, a PSI/PSIP generator 130for the mobile service, a null packet generator 140, a mobile servicemultiplexer 150, and a transport multiplexer 160. The transportmultiplexer 160 may include a main service multiplexer 161 and atransport stream (TS) packet multiplexer 162. Referring to FIG. 2, atleast one type of compression encoded main service data and the PSI/PSIPtable data generated from the PSI/PSIP generator 120 for the mainservice are inputted to the main service multiplexer 161 of thetransport multiplexer 160. The main service multiplexer 161 encapsulateseach of the inputted main service data and PSI/PSIP table data to MPEG-2TS packet forms. Then, the MPEG-2 TS packets are multiplexed andoutputted to the TS packet multiplexer 162. Herein, the data packetbeing outputted from the main service multiplexer 161 will be referredto as a main service data packet for simplicity.

Thereafter, at least one type of the compression encoded mobile servicedata and the PSI/PSIP table data generated from the PSI/PSIP generator130 for the mobile service are inputted to the mobile servicemultiplexer 150. The mobile service multiplexer 150 encapsulates each ofthe inputted mobile service data and PSI/PSIP table data to MPEG-2 TSpacket forms. Then, the MPEG-2 TS packets are multiplexed and outputtedto the TS packet multiplexer 162. Herein, the data packet beingoutputted from the mobile service multiplexer 150 will be referred to asa mobile service data packet for simplicity. At this point, thetransmitter 200 requires identification information in order to identifyand process the main service data packet and the mobile service datapacket. Herein, the identification information may use valuespre-decided in accordance with an agreement between the transmittingsystem and the receiving system, or may be configured of a separate setof data, or may modify predetermined location value with in thecorresponding data packet. As an example of the present invention, adifferent packet identifier (PID) may be assigned to identify each ofthe main service data packet and the mobile service data packet.

In another example, by modifying a synchronization data byte within aheader of the mobile service data, the service data packet may beidentified by using the synchronization data byte value of thecorresponding service data packet. For example, the synchronization byteof the main service data packet directly outputs the value decided bythe ISO/IEC13818-1 standard (i.e., 0x47) without any modification. Thesynchronization byte of the mobile service data packet modifies andoutputs the value, thereby identifying the main service data packet andthe mobile service data packet. Conversely, the synchronization byte ofthe main service data packet is modified and outputted, whereas thesynchronization byte of the mobile service data packet is directlyoutputted without being modified, thereby enabling the main service datapacket and the mobile service data packet to be identified.

A plurality of methods may be applied in the method of modifying thesynchronization byte. For example, each bit of the synchronization bytemay be inversed, or only a portion of the synchronization byte may beinversed. As described above, any type of identification information maybe used to identify the main service data packet and the mobile servicedata packet. Therefore, the scope of the present invention is notlimited only to the example set forth in the description of the presentinvention.

Meanwhile, a transport multiplexer used in the conventional digitalbroadcasting system may be used as the transport multiplexer 160according to the present invention. More specifically, in order tomultiplex the mobile service data and the main service data and totransmit the multiplexed data, the data rate of the main service islimited to a data rate of (19.39-K) Mbps. Then, K Mbps, whichcorresponds to the remaining data rate, is assigned as the data rate ofthe mobile service. Thus, the transport multiplexer which is alreadybeing used may be used as it is without any modification. Herein, thetransport multiplexer 160 multiplexes the main service data packet beingoutputted from the main service multiplexer 161 and the mobile servicedata packet being outputted from the mobile service multiplexer 150.Thereafter, the transport multiplexer 160 transmits the multiplexed datapackets to the transmitter 200.

However, in some cases, the output data rate of the mobile servicemultiplexer 150 may not be equal to K Mbps. In this case, the mobileservice multiplexer 150 multiplexes and outputs null data packetsgenerated from the null packet generator 140 so that the output datarate can reach K Mbps. More specifically, in order to match the outputdata rate of the mobile service multiplexer 150 to a constant data rate,the null packet generator 140 generates null data packets, which arethen outputted to the mobile service multiplexer 150. For example, whenthe service multiplexer 100 assigns K Mbps of the 19.39 Mbps to themobile service data, and when the remaining (19.39-K) Mbps is,therefore, assigned to the main service data, the data rate of themobile service data that are multiplexed by the service multiplexer 100actually becomes lower than K Mbps. This is because, in case of themobile service data, the pre-processor of the transmitting systemperforms additional encoding, thereby increasing the amount of data.Eventually, the data rate of the mobile service data, which may betransmitted from the service multiplexer 100, becomes smaller than KMbps.

For example, since the pre-processor of the transmitter performs anencoding process on the mobile service data at a coding rate of at least½, the amount of the data outputted from the pre-processor is increasedto more than twice the amount of the data initially inputted to thepre-processor. Therefore, the sum of the data rate of the main servicedata and the data rate of the mobile service data, both beingmultiplexed by the service multiplexer 100, becomes either equal to orsmaller than 19.39 Mbps. Therefore, in order to match the data rate ofthe data that are finally outputted from the service multiplexer 100 toa constant data rate (e.g., 19.39 Mbps), an amount of null data packetscorresponding to the amount of lacking data rate is generated from thenull packet generator 140 and outputted to the mobile servicemultiplexer 150.

Accordingly, the mobile service multiplexer 150 encapsulates each of themobile service data and the PSI/PSIP table data that are being inputtedto a MPEG-2 TS packet form. Then, the above-described TS packets aremultiplexed with the null data packets and, then, outputted to the TSpacket multiplexer 162. Thereafter, the TS packet multiplexer 162multiplexes the main service data packet being outputted from the mainservice multiplexer 161 and the mobile service data packet beingoutputted from the mobile service multiplexer 150 and transmits themultiplexed data packets to the transmitter 200 at a data rate of 19.39Mbps.

According to an embodiment of the present invention, the mobile servicemultiplexer 150 receives the null data packets. However, this is merelyexemplary and does not limit the scope of the present invention. Inother words, according to another embodiment of the present invention,the TS packet multiplexer 162 may receive the null data packets, so asto match the data rate of the finally outputted data to a constant datarate. Herein, the output path and multiplexing rule of the null datapacket is controlled by the controller 110. The controller 110 controlsthe multiplexing processed performed by the mobile service multiplexer150, the main service multiplexer 161 of the transport multiplexer 160,and the TS packet multiplexer 162, and also controls the null datapacket generation of the null packet generator 140. At this point, thetransmitter 200 discards the null data packets transmitted from theservice multiplexer 100 instead of transmitting the null data packets.

Further, in order to allow the transmitter 200 to discard the null datapackets transmitted from the service multiplexer 100 instead oftransmitting them, identification information for identifying the nulldata packet is required. Herein, the identification information may usevalues pre-decided in accordance with an agreement between thetransmitting system and the receiving system. For example, the value ofthe synchronization byte within the header of the null data packet maybe modified so as to be used as the identification information.Alternatively, a transport_error_indicator flag may also be used as theidentification information.

In the description of the present invention, an example of using thetransport_error_indicator flag as the identification information will begiven to describe an embodiment of the present invention. In this case,the transport_error_indicator flag of the null data packet is set to‘1’, and the transport_error_indicator flag of the remaining datapackets are reset to ‘0’, so as to identify the null data packet. Morespecifically, when the null packet generator 140 generates the null datapackets, if the transport_error_indicator flag from the header field ofthe null data packet is set to ‘1’ and then transmitted, the null datapacket may be identified and, therefore, be discarded. In the presentinvention, any type of identification information for identifying thenull data packets may be used. Therefore, the scope of the presentinvention is not limited only to the examples set forth in thedescription of the present invention.

According to another embodiment of the present invention, a transmissionparameter may be included in at least a portion of the null data packet,or at least one table or an operations and maintenance (OM) packet (orOMP) of the PSI/PSIP table for the mobile service. In this case, thetransmitter 200 extracts the transmission parameter and outputs theextracted transmission parameter to the corresponding block and alsotransmits the extracted parameter to the receiving system if required.More specifically, a packet referred to as an OMP is defined for thepurpose of operating and managing the transmitting system. For example,the OMP is configured in accordance with the MPEG-2 TS packet format,and the corresponding PID is given the value of 0x1FFA. The OMP isconfigured of a 4-byte header and a 184-byte payload. Herein, among the184 bytes, the first byte corresponds to an OM_type field, whichindicates the type of the OM packet.

In the present invention, the transmission parameter may be transmittedin the form of an OMP. And, in this case, among the values of thereserved fields within the OM_type field, a pre-arranged value is used,thereby indicating that the transmission parameter is being transmittedto the transmitter 200 in the form of an OMP. More specifically, thetransmitter 200 may find (or identify) the OMP by referring to the PID.Also, by parsing the OM_type field within the OMP, the transmitter 200can verify whether a transmission parameter is included after theOM_type field of the corresponding packet. The transmission parametercorresponds to supplemental data required for processing mobile servicedata from the transmitting system and the receiving system.

Herein, the transmission parameter may include data group information,region information within the data group, RS frame information, superframe information, burst information, turbo code information, and RScode information. The burst information may include burst sizeinformation, burst period information, and time information to nextburst. The burst period signifies the period at which the bursttransmitting the same mobile service is repeated. The data groupincludes a plurality of mobile service data packets, and a plurality ofsuch data groups is gathered (or grouped) to form a burst. A burstsection signifies the beginning of a current burst to the beginning of anext burst. Herein, the burst section is classified as a section thatincludes the data group (also referred to as a burst-on section), and asection that does not include the data group (also referred to as aburst-off section). A burst-on section is configured of a plurality offields, wherein one field includes one data group.

The transmission parameter may also include information on how signalsof a symbol domain are encoded in order to transmit the mobile servicedata, and multiplexing information on how the main service data and themobile service data or various types of mobile service data aremultiplexed. The information included in the transmission parameter ismerely exemplary to facilitate the understanding of the presentinvention. And, the adding and deleting of the information included inthe transmission parameter may be easily modified and changed by anyoneskilled in the art. Therefore, the present invention is not limited tothe examples proposed in the description set forth herein. Furthermore,the transmission parameters may be provided from the service multiplexer100 to the transmitter 200. Alternatively, the transmission parametersmay also be set up by an internal controller (not shown) within thetransmitter 200 or received from an external source.

Transmitter

FIG. 3 illustrates a block diagram showing an example of the transmitter200 according to an embodiment of the present invention. Herein, thetransmitter 200 includes a demultiplexer 210, a packet jitter mitigator220, a pre-processor 230, a packet multiplexer 240, a post-processor250, a synchronization (sync) multiplexer 260, and a transmission unit270. Herein, when a data packet is received from the service multiplexer100, the demultiplexer 210 should identify whether the received datapacket corresponds to a main service data packet, a mobile service datapacket, or a null data packet. For example, the demultiplexer 210 usesthe PID within the received data packet so as to identify the mainservice data packet and the mobile service data packet. Then, thedemultiplexer 210 uses a transport_error_indicator field to identify thenull data packet. The main service data packet identified by thedemultiplexer 210 is outputted to the packet jitter mitigator 220, themobile service data packet is outputted to the pre-processor 230, andthe null data packet is discarded. If a transmission parameter isincluded in the null data packet, then the transmission parameter isfirst extracted and outputted to the corresponding block. Thereafter,the null data packet is discarded.

The pre-processor 230 performs an additional encoding process of themobile service data included in the service data packet, which isdemultiplexed and outputted from the demultiplexer 210. Thepre-processor 230 also performs a process of configuring a data group sothat the data group may be positioned at a specific place in accordancewith the purpose of the data, which are to be transmitted on atransmission frame. This is to enable the mobile service data to respondswiftly and strongly against noise and channel changes. Thepre-processor 230 may also refer to the transmission parameter whenperforming the additional encoding process. Also, the pre-processor 230groups a plurality of mobile service data packets to configure a datagroup. Thereafter, known data, mobile service data, RS parity data, andMPEG header are allocated to pre-determined areas within the data group.

Pre-Processor within Transmitter

FIG. 4 illustrates a block diagram showing an example of thepre-processor 230 according to the present invention. The pre-processor230 includes a data randomizer 301, a RS frame encoder 302, a blockprocessor 303, a group formatter 304, a data deinterleaver 305, a packetformatter 306. The data randomizer 301 within the above-describedpre-processor 230 randomizes the mobile service data packet includingthe mobile service data that is inputted through the demultiplexer 210.Then, the data randomizer 301 outputs the randomized mobile service datapacket to the RS frame encoder 302. At this point, since the datarandomizer 301 performs the randomizing process on the mobile servicedata, the randomizing process that is to be performed by the datarandomizer 251 of the post-processor 250 on the mobile service data maybe omitted. The data randomizer 301 may also discard the synchronizationbyte within the mobile service data packet and perform the randomizingprocess. This is an option that may be chosen by the system designer. Inthe example given in the present invention, the randomizing process isperformed without discarding the synchronization byte within the mobileservice data packet.

The RS frame encoder 302 groups a plurality of mobile thesynchronization byte within the mobile service data packets that israndomized and inputted, so as to create a RS frame. Then, the RS frameencoder 302 performs at least one of an error correction encodingprocess and an error detection encoding process in RS frame units.Accordingly, robustness may be provided to the mobile service data,thereby scattering group error that may occur during changes in afrequency environment, thereby enabling the enhanced data to respond tothe frequency environment, which is extremely vulnerable and liable tofrequent changes. Also, the RS frame encoder 302 groups a plurality ofRS frame so as to create a super frame, thereby performing a rowpermutation process in super frame units. The row permutation processmay also be referred to as a row interleaving process. Hereinafter, theprocess will be referred to as row permutation for simplicity.

More specifically, when the RS frame encoder 302 performs the process ofpermuting each row of the super frame in accordance with apre-determined rule, the position of the rows within the super framebefore and after the row permutation process is changed. If the rowpermutation process is performed by super frame units, and even thoughthe section having a plurality of errors occurring therein becomes verylong, and even though the number of errors included in the RS frame,which is to be decoded, exceeds the extent of being able to becorrected, the errors become dispersed within the entire super frame.Thus, the decoding ability is even more enhanced as compared to a singleRS frame.

At this point, as an example of the present invention, RS-encoding isapplied for the error correction encoding process, and a cyclicredundancy check (CRC) encoding is applied for the error detectionprocess. When performing the RS-encoding, parity data that are used forthe error correction are generated. And, when performing the CRCencoding, CRC data that are used for the error detection are generated.The RS encoding is one of forward error correction (FEC) methods. TheFEC corresponds to a technique for compensating errors that occur duringthe transmission process. The CRC data generated by CRC encoding may beused for indicating whether or not the mobile service data have beendamaged by the errors while being transmitted through the channel. Inthe present invention, a variety of error detection coding methods otherthan the CRC encoding method may be used, or the error correction codingmethod may be used to enhance the overall error correction ability ofthe receiving system. Herein, the RS frame encoder 302 refers to apre-determined transmission parameter and/or the transmission parameterprovided from the service multiplexer 100 so as to perform operationsincluding RS frame configuration, RS encoding, CRC encoding, super frameconfiguration, and row permutation in super frame units.

Pre-Processor within RS Frame Encoder

FIG. 5( a) to FIG. 5( e) illustrate error correction encoding and errordetection encoding processed according to an embodiment of the presentinvention. More specifically, the RS frame encoder 302 first divides theinputted mobile service data bytes to units of a predetermined length.The predetermined length is decided by the system designer. And, in theexample of the present invention, the predetermined length is equal to187 bytes, and, therefore, the 187-byte unit will be referred to as apacket for simplicity. For example, when the mobile service data thatare being inputted, as shown in FIG. 5( a), correspond to a MPEGtransport packet stream configured of 188-byte units, the firstsynchronization byte is removed, as shown in FIG. 5( b), so as toconfigure a 187-byte unit. Herein, the synchronization byte is removedbecause each mobile service data packet has the same value.

Herein, the process of removing the synchronization byte may beperformed during a randomizing process of the data randomizer 301 in anearlier process. In this case, the process of the removing thesynchronization byte by the RS frame encoder 302 may be omitted.Moreover, when adding synchronization bytes from the receiving system,the process may be performed by the data derandomizer instead of the RSframe decoder. Therefore, if a removable fixed byte (e.g.,synchronization byte) does not exist within the mobile service datapacket that is being inputted to the RS frame encoder 302, or if themobile service data that are being inputted are not configured in apacket format, the mobile service data that are being inputted aredivided into 187-byte units, thereby configuring a packet for each187-byte unit.

Subsequently, as shown in FIG. 5( c), N number of packets configured of187 bytes is grouped to configure a RS frame. At this point, the RSframe is configured as a RS frame having the size of N(row)*187(column)bytes, in which 187-byte packets are sequentially inputted in a rowdirection. In order to simplify the description of the presentinvention, the RS frame configured as described above will also bereferred to as a first RS frame. More specifically, only pure mobileservice data are included in the first RS frame, which is the same asthe structure configured of 187 N-byte rows. Thereafter, the mobileservice data within the RS frame are divided into an equal size. Then,when the divided mobile service data are transmitted in the same orderas the input order for configuring the RS frame, and when one or moreerrors have occurred at a particular point during thetransmitting/receiving process, the errors are clustered (or gathered)within the RS frame as well. In this case, the receiving system uses aRS erasure decoding method when performing error correction decoding,thereby enhancing the error correction ability. At this point, the Nnumber of columns within the N number of RS frame includes 187 bytes, asshown in FIG. 5( c).

In this case, a (Nc,Kc)−RS encoding process is performed on each column,so as to generate Nc−Kc(=P) number of parity bytes. Then, the newlygenerated P number of parity bytes is added after the very last byte ofthe corresponding column, thereby creating a column of (187+P) bytes.Herein, as shown in FIG. 5( c), Kc is equal to 187 (i.e., Kc=187), andNc is equal to 187+P (i.e., Nc=187+P). For example, when P is equal to48, (235,187)-RS encoding process is performed so as to create a columnof 235 bytes. When such RS encoding process is performed on all N numberof columns, as shown in FIG. 5( c), a RS frame having the size ofN(row)*(187+P)(column) bytes may be created, as shown in FIG. 5( d). Inorder to simplify the description of the present invention, the RS framehaving the RS parity inserted therein will be referred to as s second RSframe. More specifically, the second RS frame having the structure of(187+P) rows configured of N bytes may be configured.

As shown in FIG. 5( c) or FIG. 5( d), each row of the RS frame isconfigured of N bytes. However, depending upon channel conditionsbetween the transmitting system and the receiving system, error may beincluded in the RS frame. When errors occur as described above, CRC data(or CRC code or CRC checksum) may be used on each row unit in order toverify whether error exists in each row unit. The RS frame encoder 302may perform CRC encoding on the mobile service data being RS encoded soas to create (or generate) the CRC data. The CRC data being generated byCRC encoding may be used to indicate whether the mobile service datahave been damaged while being transmitted through the channel.

The present invention may also use different error detection encodingmethods other than the CRC encoding method. Alternatively, the presentinvention may use the error correction encoding method to enhance theoverall error correction ability of the receiving system. FIG. 5( e)illustrates an example of using a 2-byte (i.e., 16-bit) CRC checksum asthe CRC data. Herein, a 2-byte CRC checksum is generated for N number ofbytes of each row, thereby adding the 2-byte CRC checksum at the end ofthe N number of bytes. Thus, each row is expanded to (N+2) number ofbytes. Equation 1 below corresponds to an exemplary equation forgenerating a 2-byte CRC checksum for each row being configured of Nnumber of bytes.g(x)=x ¹⁶ +x ¹² +x ⁵+1  Equation 1

The process of adding a 2-byte checksum in each row is only exemplary.Therefore, the present invention is not limited only to the exampleproposed in the description set forth herein. In order to simplify theunderstanding of the present invention, the RS frame having the RSparity and CRC checksum added therein will hereinafter be referred to asa third RS frame. More specifically, the third RS frame corresponds to(187+P) number of rows each configured of (N+2) number of bytes. Asdescribed above, when the process of RS encoding and CRC encoding arecompleted, the (N*187)-byte RS frame is expanded to a (N+2)(187+P)-byteRS frame. Furthermore, the RS frame that is expanded, as shown in FIG.5( e), is inputted to the block processor 303.

As described above, the mobile service data encoded by the RS frameencoder 302 are inputted to the block processor 303. The block processor303 then encodes the inputted mobile service data at a coding rate ofG/H (wherein, G is smaller than H (i.e., G<H)) and then outputted to thegroup formatter 304. More specifically, the block processor 303 dividesthe mobile service data being inputted in byte units into bit units.Then, the G number of bits is encoded to H number of bits. Thereafter,the encoded bits are converted back to byte units and then outputted.For example, if 1 bit of the input data is coded to 2 bits andoutputted, then G is equal to 1 and H is equal to 2 (i.e., G=1 and H=2).Alternatively, if 1 bit of the input data is coded to 4 bits andoutputted, then G is equal to 1 and H is equal to 4 (i.e., G=1 and H=4).Hereinafter, the former coding rate will be referred to as a coding rateof ½ (½-rate coding), and the latter coding rate will be referred to asa coding rate of ¼ (¼-rate coding), for simplicity.

Herein, when using the ¼ coding rate, the coding efficiency is greaterthan when using the ½ coding rate, and may, therefore, provide greaterand enhanced error correction ability. For such reason, when it isassumed that the data encoded at a ¼ coding rate in the group formatter304, which is located near the end portion of the system, are allocatedto an area in which the receiving performance may be deteriorated, andthat the data encoded at a ½ coding rate are allocated to an area havingexcellent receiving performance, the difference in performance may bereduced. At this point, the block processor 303 may also receivesignaling information including transmission parameters. Herein, thesignaling information may also be processed with either ½-rate coding or¼-rate coding as in the step of processing mobile service data.Thereafter, the signaling information is also considered the same as themobile service data and processed accordingly.

Meanwhile, the group formatter inserts mobile service data that areoutputted from the block processor 303 in corresponding areas within adata group, which is configured in accordance with a pre-defined rule.Also, with respect to the data deinterleaving process, each place holderor known data (or known data place holders) are also inserted incorresponding areas within the data group. At this point, the data groupmay be divided into at least one hierarchical area. Herein, the type ofmobile service data being inserted in each area may vary depending uponthe characteristics of each hierarchical area. Additionally, each areamay, for example, be divided based upon the receiving performance withinthe data group. Furthermore, one data group may be configured to includea set of field synchronization data.

In an example given in the present invention, a data group is dividedinto A, B, and C regions in a data configuration prior to datadeinterleaving. At this point, the group formatter 304 allocates themobile service data, which are inputted after being RS encoded and blockencoded, to each of the corresponding regions by referring to thetransmission parameter. FIG. 6A illustrates an alignment of data afterbeing data interleaved and identified, and FIG. 6B illustrates analignment of data before being data interleaved and identified. Morespecifically, a data structure identical to that shown in FIG. 6A istransmitted to a receiving system. Also, the data group configured tohave the same structure as the data structure shown in FIG. 6A isinputted to the data deinterleaver 305.

As described above, FIG. 6A illustrates a data structure prior to datadeinterleaving that is divided into 3 regions, such as region A, regionB, and region C. Also, in the present invention, each of the regions Ato C is further divided into a plurality of regions. Referring to FIG.6A, region A is divided into 5 regions (A1 to A5), region B is dividedinto 2 regions (B1 and B2), and region C is divided into 3 regions (C1to C3). Herein, regions A to C are identified as regions having similarreceiving performances within the data group. Herein, the type of mobileservice data, which are inputted, may also vary depending upon thecharacteristic of each region.

In the example of the present invention, the data structure is dividedinto regions A to C based upon the level of interference of the mainservice data. Herein, the data group is divided into a plurality ofregions to be used for different purposes. More specifically, a regionof the main service data having no interference or a very lowinterference level may be considered to have a more resistant (orstronger) receiving performance as compared to regions having higherinterference levels. Additionally, when using a system inserting andtransmitting known data in the data group, and when consecutively longknown data are to be periodically inserted in the mobile service data,the known data having a predetermined length may be periodicallyinserted in the region having no interference from the main service data(e.g., region A). However, due to interference from the main servicedata, it is difficult to periodically insert known data and also toinsert consecutively long known data to a region having interferencefrom the main service data (e.g., region B and region C).

Hereinafter, examples of allocating data to region A (A1 to A5), regionB (B1 and B2), and region C (C1 to C3) will now be described in detailwith reference to FIG. 6A. The data group size, the number ofhierarchically divided regions within the data group and the size ofeach region, and the number of mobile service data bytes that can beinserted in each hierarchically divided region of FIG. 6A are merelyexamples given to facilitate the understanding of the present invention.Herein, the group formatter 304 creates a data group including places inwhich field synchronization data bytes are to be inserted, so as tocreate the data group that will hereinafter be described in detail.

More specifically, region A is a region within the data group in which along known data sequence may be periodically inserted, and in whichincludes regions wherein the main service data are not mixed (e.g., A1to A5). Also, region A includes a region (e.g., A1) located between afield synchronization region and the region in which the first knowndata sequence is to be inserted. The field synchronization region hasthe length of one segment (i.e., 832 symbols) existing in an ATSCsystem.

For example, referring to FIG. 6A, 2428 bytes of the mobile service datamay be inserted in region A1, 2580 bytes may be inserted in region A2,2772 bytes may be inserted in region A3, 2472 bytes may be inserted inregion A4, and 2772 bytes may be inserted in region A5. Herein, trellisinitialization data or known data, MPEG header, and RS parity are notincluded in the mobile service data. As described above, when region Aincludes a known data sequence at both ends, the receiving system useschannel information that can obtain known data or field synchronizationdata, so as to perform equalization, thereby providing enforcedequalization performance.

Also, region B includes a region located within 8 segments at thebeginning of a field synchronization region within the data group(chronologically placed before region A1) (e.g., region B1), and aregion located within 8 segments behind the very last known datasequence which is inserted in the data group (e.g., region B2). Forexample, 930 bytes of the mobile service data may be inserted in theregion B1, and 1350 bytes may be inserted in region B2. Similarly,trellis initialization data or known data, MPEG header, and RS parityare not included in the mobile service data. In case of region B, thereceiving system may perform equalization by using channel informationobtained from the field synchronization region. Alternatively, thereceiving system may also perform equalization by using channelinformation that may be obtained from the last known data sequence,thereby enabling the system to respond to the channel changes.

Region C includes a region located within 30 segments including andpreceding the 9^(th) segment of the field synchronization region(chronologically located before region A) (e.g., region C1), a regionlocated within 12 segments including and following the 9^(th) segment ofthe very last known data sequence within the data group (chronologicallylocated after region A) (e.g., region C2), and a region located in 32segments after the region C2 (e.g., region C3). For example, 1272 bytesof the mobile service data may be inserted in the region C1, 1560 bytesmay be inserted in region C2, and 1312 bytes may be inserted in regionC3. Similarly, trellis initialization data or known data, MPEG header,and RS parity are not included in the mobile service data. Herein,region C (e.g., region C1) is located chronologically earlier than (orbefore) region A.

Since region C (e.g., region C1) is located further apart from the fieldsynchronization region which corresponds to the closest known dataregion, the receiving system may use the channel information obtainedfrom the field synchronization data when performing channelequalization. Alternatively, the receiving system may also use the mostrecent channel information of a previous data group. Furthermore, inregion C (e.g., region C2 and region C3) located before region A, thereceiving system may use the channel information obtained from the lastknown data sequence to perform equalization. However, when the channelsare subject to fast and frequent changes, the equalization may not beperformed perfectly. Therefore, the equalization performance of region Cmay be deteriorated as compared to that of region B.

When it is assumed that the data group is allocated with a plurality ofhierarchically divided regions, as described above, the block processor303 may encode the mobile service data, which are to be inserted to eachregion based upon the characteristic of each hierarchical region, at adifferent coding rate. For example, the block processor 303 may encodethe mobile service data, which are to be inserted in regions A1 to A5 ofregion A, at a coding rate of ½. Then, the group formatter 304 mayinsert the ½-rate encoded mobile service data to regions A1 to A5.

The block processor 303 may encode the mobile service data, which are tobe inserted in regions B1 and B2 of region B, at a coding rate of ¼having higher error correction ability as compared to the ½-coding rate.Then, the group formatter 304 inserts the ¼-rate coded mobile servicedata in region B1 and region B2. Furthermore, the block processor 303may encode the mobile service data, which are to be inserted in regionsC1 to C3 of region C, at a coding rate of ¼ or a coding rate havinghigher error correction ability than the ¼-coding rate. Then, the groupformatter 304 may either insert the encoded mobile service data toregions C1 to C3, as described above, or leave the data in a reservedregion for future usage.

In addition, the group formatter 304 also inserts supplemental data,such as signaling information that notifies the overall transmissioninformation, other than the mobile service data in the data group. Also,apart from the encoded mobile service data outputted from the blockprocessor 303, the group formatter 304 also inserts MPEG header placeholders, non-systematic RS parity place holders, main service data placeholders, which are related to data deinterleaving in a later process, asshown in FIG. 6A. Herein, the main service data place holders areinserted because the mobile service data bytes and the main service databytes are alternately mixed with one another in regions B and C basedupon the input of the data deinterleaver, as shown in FIG. 6A. Forexample, based upon the data outputted after data deinterleaving, theplace holder for the MPEG header may be allocated at the very beginningof each packet.

Furthermore, the group formatter 304 either inserts known data generatedin accordance with a pre-determined method or inserts known data placeholders for inserting the known data in a later process. Additionally,place holders for initializing the trellis encoding module 256 are alsoinserted in the corresponding regions. For example, the initializationdata place holders may be inserted in the beginning of the known datasequence. Herein, the size of the mobile service data that can beinserted in a data group may vary in accordance with the sizes of thetrellis initialization place holders or known data (or known data placeholders), MPEG header place holders, and RS parity place holders.

The output of the group formatter 304 is inputted to the datadeinterleaver 305. And, the data deinterleaver 305 deinterleaves data byperforming an inverse process of the data interleaver on the data andplace holders within the data group, which are then outputted to thepacket formatter 306. More specifically, when the data and place holderswithin the data group configured, as shown in FIG. 6A, are deinterleavedby the data deinterleaver 305, the data group being outputted to thepacket formatter 306 is configured to have the structure shown in FIG.6B.

The packet formatter 306 removes the main service data place holders andthe RS parity place holders that were allocated for the deinterleavingprocess from the deinterleaved data being inputted. Then, the packetformatter 306 groups the remaining portion and replaces the 4-byte MPEGheader place holder with an MPEG header having a null packet PID (or anunused PID from the main service data packet). Also, when the groupformatter 304 inserts known data place holders, the packet formatter 306may insert actual known data in the known data place holders, or maydirectly output the known data place holders without any modification inorder to make replacement insertion in a later process. Thereafter, thepacket formatter 306 identifies the data within the packet-formatteddata group, as described above, as a 188-byte unit mobile service datapacket (i.e., MPEG TS packet), which is then provided to the packetmultiplexer 240.

The packet multiplexer 240 multiplexes the mobile service data packetoutputted from the pre-processor 230 and the main service data packetoutputted from the packet jitter mitigator 220 in accordance with apre-defined multiplexing method. Then, the packet multiplexer 240outputs the multiplexed data packets to the data randomizer 251 of thepost-processor 250. Herein, the multiplexing method may vary inaccordance with various variables of the system design. One of themultiplexing methods of the packet formatter 240 consists of providing aburst section along a time axis, and, then, transmitting a plurality ofdata groups during a burst-on section within the burst section, andtransmitting only the main service data during the burst-off sectionwithin the burst section. Herein, the burst section indicates thesection starting from the beginning of the current burst until thebeginning of the next burst.

At this point, the main service data may be transmitted during theburst-on section. The packet multiplexer 240 refers to the transmissionparameter, such as information on the burst size or the burst period, soas to be informed of the number of data groups and the period of thedata groups included in a single burst. Herein, the mobile service dataand the main service data may co-exist in the burst-on section, and onlythe main service data may exist in the burst-off section. Therefore, amain data service section transmitting the main service data may existin both burst-on and burst-off sections. At this point, the main dataservice section within the burst-on section and the number of main dataservice packets included in the burst-off section may either bedifferent from one another or be the same.

When the mobile service data are transmitted in a burst structure, inthe receiving system receiving only the mobile service data turns thepower on only during the burst section, thereby receiving thecorresponding data. Alternatively, in the section transmitting only themain service data, the power is turned off so that the main service dataare not received in this section. Thus, the power consumption of thereceiving system may be reduced.

Detailed Embodiments of the RS Frame Structure and Packet Multiplexing

Hereinafter, detailed embodiments of the pre-processor 230 and thepacket multiplexer 240 will now be described. According to an embodimentof the present invention, the N value corresponding to the length of arow, which is included in the RS frame that is configured by the RSframe encoder 302, is set to 538. Accordingly, the RS frame encoder 302receives 538 transport stream (TS) packets so as to configure a first RSframe having the size of 538*187 bytes. Thereafter, as described above,the first RS frame is processed with a (235,187)-RS encoding process soas to configure a second RS frame having the size of 538*235 bytes.Finally, the second RS frame is processed with generating a 16-bitchecksum so as to configure a third RS frame having the sizes of540*235.

Meanwhile, as shown in FIG. 6A, the sum of the number of bytes ofregions A1 to A5 of region A, in which ½-rate encoded mobile servicedata are to be inserted, among the plurality of regions within the datagroup is equal to 13024 bytes (=2428+2580+2772+2472+2772 bytes). Herein,the number of byte prior to performing the ½-rate encoding process isequal to 6512 (=13024/2). On the other hand, the sum of the number ofbytes of regions B1 and B2 of region B, in which ¼-rate encoded mobileservice data are to be inserted, among the plurality of regions withinthe data group is equal to 2280 bytes (=930+1350 bytes). Herein, thenumber of byte prior to performing the ¼-rate encoding process is equalto 570 (=2280/4).

In other words, when 7082 bytes of mobile service data are inputted tothe block processor 303, 6512 byte are expanded to 13024 bytes by being½-rate encoded, and 570 bytes are expanded to 2280 bytes by being ¼-rateencoded. Thereafter, the block processor 303 inserts the mobile servicedata expanded to 13024 bytes in regions A1 to A5 of region A and, also,inserts the mobile service data expanded to 2280 bytes in regions B1 andB2 of region B. Herein, the 7082 bytes of mobile service data beinginputted to the block processor 303 may be divided into an output of theRS frame encoder 302 and signaling information. In the presentinvention, among the 7082 bytes of mobile service data, 7050 bytescorrespond to the output of the RS frame encoder 302, and the remaining32 bytes correspond to the signaling information data. Then, ½-rateencoding or ¼-rate encoding is performed on the corresponding databytes.

Meanwhile, a RS frame being processed with RS encoding and CRC encodingfrom the RS frame encoder 302 is configured of 540*235 bytes, in otherwords, 126900 bytes. The 126900 bytes are divided by 7050-byte unitsalong the time axis, so as to produce 18 7050-byte units. Thereafter, a32-byte unit of signaling information data is added to the 7050-byteunit mobile service data being outputted from the RS frame encoder 302.Subsequently, the RS frame encoder 302 performs ½-rate encoding or¼-rate encoding on the corresponding data bytes, which are thenoutputted to the group formatter 304. Accordingly, the group formatter304 inserts the ½-rate encoded data in region A and the ¼-rate encodeddata in region B.

The process of deciding an N value that is required for configuring theRS frame from the RS frame encoder 302 will now be described in detail.More specifically, the size of the final RS frame (i.e., the third RSframe), which is RS encoded and CRC encoded from the RS frame encoder302, which corresponds to (N+2)*235 bytes should be allocated to Xnumber of groups, wherein X is an integer. Herein, in a single datagroup, 7050 data bytes prior to being encoded are allocated. Therefore,if the (N+2)*235 bytes are set to be the exact multiple of7050(=30*235), the output data of the RS frame encoder 302 may beefficiently allocated to the data group. According to an embodiment ofthe present invention, the value of N is decided so that (N+2) becomes amultiple of 30. For example, in the present invention, N is equal to538, and (N+2)(=540) divided by 30 is equal to 18. This indicates thatthe mobile service data within one RS frame are processed with either½-rate encoding or ¼-rate encoding. The encoded mobile service data arethen allocated to 18 data groups.

FIG. 7 illustrates a process of dividing the RS frame according to thepresent invention. More specifically, the RS frame having the size of(N+2)*235 is divided into 30*235 byte blocks. Then, the divided blocksare mapped to a single group. In other words, the data of a block havingthe size of 30*235 bytes are processed with one of a ½-rate encodingprocess and a ¼-rate encoding process and are, then, inserted in a datagroup. Thereafter, the data group having corresponding data and placeholders inserted in each hierarchical region divided by the groupformatter 304 passes through the data deinterleaver 305 and the packetformatter 306 so as to be inputted to the packet multiplexer 240.

FIG. 8 illustrates exemplary operations of a packet multiplexer fortransmitting the data group according to the present invention. Morespecifically, the packet multiplexer 240 multiplexes a field including adata group, in which the mobile service data and main service data aremixed with one another, and a field including only the main servicedata. Thereafter, the packet multiplexer 240 outputs the multiplexedfields to the data randomizer 251. At this point, in order to transmitthe RS frame having the size of 540*235 bytes, 18 data groups should betransmitted. Herein, each data group includes field synchronizationdata, as shown in FIG. 6A. Therefore, the 18 data groups are transmittedduring 18 field sections, and the section during which the 18 datagroups are being transmitted corresponds to the burst-on section.

In each field within the burst-on section, a data group including fieldsynchronization data is multiplexed with main service data, which arethen outputted. For example, in the embodiment of the present invention,in each field within the burst-on section, a data group having the sizeof 118 segments is multiplexed with a set of main service data havingthe size of 194 segments. Referring to FIG. 8, during the burst-onsection (i.e., during the 18 field sections), a field including 18 datagroups is transmitted. Then, during the burst-off section that follows(i.e., during the 12 field sections), a field consisting only of themain service data is transmitted. Subsequently, during a subsequentburst-on section, 18 fields including 18 data groups are transmitted.And, during the following burst-off section, 12 fields consisting onlyof the main service data are transmitted.

Furthermore, in the present invention, the same type of data service maybe provided in the first burst-on section including the first 18 datagroups and in the second burst-on section including the next 18 datagroups. Alternatively, different types of data service may be providedin each burst-on section. For example, when it is assumed that differentdata service types are provided to each of the first burst-on sectionand the second burst-on section, and that the receiving system wishes toreceive only one type of data service, the receiving system turns thepower on only during the corresponding burst-on section including thedesired data service type so as to receive the corresponding 18 datafields. Then, the receiving system turns the power off during theremaining 42 field sections so as to prevent other data service typesfrom being received. Thus, the amount of power consumption of thereceiving system may be reduced. In addition, the receiving systemaccording to the present invention is advantageous in that one RS framemay be configured from the 18 data groups that are received during asingle burst-on section.

According to the present invention, the number of data groups includedin a burst-on section may vary based upon the size of the RS frame, andthe size of the RS frame varies in accordance with the value N. Morespecifically, by adjusting the value N, the number of data groups withinthe burst section may be adjusted. Herein, in an example of the presentinvention, the (235,187)-RS encoding process adjusts the value N duringa fixed state. Furthermore, the size of the mobile service data that canbe inserted in the data group may vary based upon the sizes of thetrellis initialization data or known data, the MPEG header, and the RSparity, which are inserted in the corresponding data group.

Meanwhile, since a data group including mobile service data in-betweenthe data bytes of the main service data during the packet multiplexingprocess, the shifting of the chronological position (or place) of themain service data packet becomes relative. Also, a system object decoder(i.e., MPEG decoder) for processing the main service data of thereceiving system, receives and decodes only the main service data andrecognizes the mobile service data packet as a null data packet.Therefore, when the system object decoder of the receiving systemreceives a main service data packet that is multiplexed with the datagroup, a packet jitter occurs.

At this point, since a multiple-level buffer for the video data existsin the system object decoder and the size of the buffer is relativelylarge, the packet jitter generated from the packet multiplexer 240 doesnot cause any serious problem in case of the video data. However, sincethe size of the buffer for the audio data is relatively small, thepacket jitter may cause considerable problem. More specifically, due tothe packet jitter, an overflow or underflow may occur in the buffer forthe main service data of the receiving system (e.g., the buffer for theaudio data). Therefore, the packet jitter mitigator 220 re-adjusts therelative position of the main service data packet so that the overflowor underflow does not occur in the system object decoder.

In the present invention, examples of repositioning places for the audiodata packets within the main service data in order to minimize theinfluence on the operations of the audio buffer will be described indetail. The packet jitter mitigator 220 repositions the audio datapackets in the main service data section so that the audio data packetsof the main service data can be as equally and uniformly aligned andpositioned as possible. The standard for repositioning the audio datapackets in the main service data performed by the packet jittermitigator 220 will now be described. Herein, it is assumed that thepacket jitter mitigator 220 knows the same multiplexing information asthat of the packet multiplexer 240, which is placed further behind thepacket jitter mitigator 220.

Firstly, if one audio data packet exists in the main service datasection (e.g., the main service data section positioned between two datagroups) within the burst-on section, the audio data packet is positionedat the very beginning of the main service data section. Alternatively,if two audio data packets exist in the corresponding data section, oneaudio data packet is positioned at the very beginning and the otheraudio data packet is positioned at the very end of the main service datasection. Further, if more than three audio data packets exist, one audiodata packet is positioned at the very beginning of the main service datasection, another is positioned at the very end of the main service datasection, and the remaining audio data packets are equally positionedbetween the first and last audio data packets. Secondly, during the mainservice data section placed immediately before the beginning of aburst-on section (i.e., during a burst-off section), the audio datapacket is placed at the very end of the corresponding section.

Thirdly, during a main service data section within the burst-off sectionafter the burst-on section, the audio data packet is positioned at thevery end of the main service data section. Finally, the data packetsother than audio data packets are positioned in accordance with theinputted order in vacant spaces (i.e., spaces that are not designatedfor the audio data packets). Meanwhile, when the positions of the mainservice data packets are relatively re-adjusted, associated programclock reference (PCR) values may also be modified accordingly. The PCRvalue corresponds to a time reference value for synchronizing the timeof the MPEG decoder. Herein, the PCR value is inserted in a specificregion of a TS packet and then transmitted.

In the example of the present invention, the packet jitter mitigator 220also performs the operation of modifying the PCR value. The output ofthe packet jitter mitigator 220 is inputted to the packet multiplexer240. As described above, the packet multiplexer 240 multiplexes the mainservice data packet outputted from the packet jitter mitigator 220 withthe mobile service data packet outputted from the pre-processor 230 intoa burst structure in accordance with a pre-determined multiplexing rule.Then, the packet multiplexer 240 outputs the multiplexed data packets tothe data randomizer 251 of the post-processor 250.

If the inputted data correspond to the main service data packet, thedata randomizer 251 performs the same randomizing process as that of theconventional randomizer. More specifically, the synchronization bytewithin the main service data packet is deleted. Then, the remaining 187data bytes are randomized by using a pseudo random byte generated fromthe data randomizer 251. Thereafter, the randomized data are outputtedto the RS encoder/non-systematic RS encoder 252.

On the other hand, if the inputted data correspond to the mobile servicedata packet, the data randomizer 251 may randomize only a portion of thedata packet. For example, if it is assumed that a randomizing processhas already been performed in advance on the mobile service data packetby the pre-processor 230, the data randomizer 251 deletes thesynchronization byte from the 4-byte MPEG header included in the mobileservice data packet and, then, performs the randomizing process only onthe remaining 3 data bytes of the MPEG header. Thereafter, therandomized data bytes are outputted to the RS encoder/non-systematic RSencoder 252. More specifically, the randomizing process is not performedon the remaining portion of the mobile service data excluding the MPEGheader. In other words, the remaining portion of the mobile service datapacket is directly outputted to the RS encoder/non-systematic RS encoder252 without being randomized. Also, the data randomizer 251 may or maynot perform a randomizing process on the known data (or known data placeholders) and the initialization data place holders included in themobile service data packet.

The RS encoder/non-systematic RS encoder 252 performs an RS encodingprocess on the data being randomized by the data randomizer 251 or onthe data bypassing the data randomizer 251, so as to add 20 bytes of RSparity data. Thereafter, the processed data are outputted to the datainterleaver 253. Herein, if the inputted data correspond to the mainservice data packet, the RS encoder/non-systematic RS encoder 252performs the same systematic RS encoding process as that of theconventional broadcasting system, thereby adding the 20-byte RS paritydata at the end of the 187-byte data. Alternatively, if the inputteddata correspond to the mobile service data packet, the RSencoder/non-systematic RS encoder 252 performs a non-systematic RSencoding process. At this point, the 20-byte RS parity data obtainedfrom the non-systematic RS encoding process are inserted in apre-decided parity byte place within the mobile service data packet.

The data interleaver 253 corresponds to a byte unit convolutionalinterleaver. The output of the data interleaver 253 is inputted to theparity replacer 254 and to the non-systematic RS encoder 255. Meanwhile,a process of initializing a memory within the trellis encoding module256 is primarily required in order to decide the output data of thetrellis encoding module 256, which is located after the parity replacer254, as the known data pre-defined according to an agreement between thereceiving system and the transmitting system. More specifically, thememory of the trellis encoding module 256 should first be initializedbefore the received known data sequence is trellis-encoded. At thispoint, the beginning portion of the known data sequence that is receivedcorresponds to the initialization data place holder and not to theactual known data. Herein, the initialization data place holder has beenincluded in the data by the group formatter within the pre-processor 230in an earlier process. Therefore, the process of generatinginitialization data and replacing the initialization data place holderof the corresponding memory with the generated initialization data arerequired to be performed immediately before the inputted known datasequence is trellis-encoded.

Additionally, a value of the trellis memory initialization data isdecided and generated based upon a memory status of the trellis encodingmodule 256. Further, due to the newly replaced initialization data, aprocess of newly calculating the RS parity and replacing the RS parity,which is outputted from the data interleaver 253, with the newlycalculated RS parity is required. Therefore, the non-systematic RSencoder 255 receives the mobile service data packet including theinitialization data place holders, which are to be replaced with theactual initialization data, from the data interleaver 253 and alsoreceives the initialization data from the trellis encoding module 256.

Among the inputted mobile service data packet, the initialization dataplace holders are replaced with the initialization data, and the RSparity data that are added to the mobile service data packet are removedand processed with non-systematic RS encoding. Thereafter, the new RSparity obtained by performing the non-systematic RS encoding process isoutputted to the parity replacer 255. Accordingly, the parity replacer255 selects the output of the data interleaver 253 as the data withinthe mobile service data packet, and the parity replacer 255 selects theoutput of the non-systematic RS encoder 255 as the RS parity. Theselected data are then outputted to the trellis encoding module 256.

Meanwhile, if the main service data packet is inputted or if the mobileservice data packet, which does not include any initialization dataplace holders that are to be replaced, is inputted, the parity replacer254 selects the data and RS parity that are outputted from the datainterleaver 253. Then, the parity replacer 254 directly outputs theselected data to the trellis encoding module 256 without anymodification. The trellis encoding module 256 converts the byte-unitdata to symbol units and performs a 12-way interleaving process so as totrellis-encode the received data. Thereafter, the processed data areoutputted to the synchronization multiplexer 260.

The synchronization multiplexer 260 inserts a field synchronizationsignal and a segment synchronization signal to the data outputted fromthe trellis encoding module 256 and, then, outputs the processed data tothe pilot inserter 271 of the transmission unit 270. Herein, the datahaving a pilot inserted therein by the pilot inserter 271 are modulatedby the modulator 272 in accordance with a pre-determined modulatingmethod (e.g., a VSB method). Thereafter, the modulated data aretransmitted to each receiving system though the radio frequency (RF)up-converter 273.

Block Processor

FIG. 9 illustrates a block diagram showing a structure of a blockprocessor according to the present invention. Herein, the blockprocessor includes a byte-bit converter 401, a symbol encoder 402, asymbol interleaver 403, and a symbol-byte converter 404. The byte-bitconverter 401 divides the mobile service data bytes that are inputtedfrom the RS frame encoder 112 into bits, which are then outputted to thesymbol encoder 402. The byte-bit converter 401 may also receivesignaling information including transmission parameters. The signalinginformation data bytes are also divided into bits so as to be outputtedto the symbol encoder 402. Herein, the signaling information includingtransmission parameters may be processed with the same data processingstep as that of the mobile service data. More specifically, thesignaling information may be inputted to the block processor 303 bypassing through the data randomizer 301 and the RS frame encoder 302.Alternatively, the signaling information may also be directly outputtedto the block processor 303 without passing though the data randomizer301 and the RS frame encoder 302.

The symbol encoder 402 corresponds to a G/H-rate encoder encoding theinputted data from G bits to H bits and outputting the data encoded atthe coding rate of G/H. According to the embodiment of the presentinvention, it is assumed that the symbol encoder 402 performs either acoding rate of ½ (also referred to as a ½-rate encoding process) or anencoding process at a coding rate of ¼ (also referred to as a ¼-rateencoding process). The symbol encoder 402 performs one of ½-rateencoding and ¼-rate encoding on the inputted mobile service data andsignaling information. Thereafter, the signaling information is alsorecognized as the mobile service data and processed accordingly.

In case of performing the ½-rate coding process, the symbol encoder 402receives 1 bit and encodes the received 1 bit to 2 bits (i.e., 1symbol). Then, the symbol encoder 402 outputs the processed 2 bits (or 1symbol). On the other hand, in case of performing the ¼-rate encodingprocess, the symbol encoder 402 receives 1 bit and encodes the received1 bit to 4 bits (i.e., 2 symbols). Then, the symbol encoder 402 outputsthe processed 4 bits (or 2 symbols).

FIG. 10 illustrates a detailed block diagram of the symbol encoder 402shown in FIG. 9. The symbol encoder 402 includes two delay units 501 and503 and three adders 502, 504, and 505. Herein, the symbol encoder 402encodes an input data bit U and outputs the coded bit U to 4 bits (u0 tou4). At this point, the data bit U is directly outputted as uppermostbit u0 and simultaneously encoded as lower bit u1u2u3 and thenoutputted. More specifically, the input data bit U is directly outputtedas the uppermost bit u0 and simultaneously outputted to the first andthird adders 502 and 505. The first adder 502 adds the input data bit Uand the output bit of the first delay unit 501 and, then, outputs theadded bit to the second delay unit 503. Then, the data bit delayed by apre-determined time (e.g., by 1 clock) in the second delay unit 503 isoutputted as lower bit u1 and simultaneously fed-back to the first delayunit 501. The first delay unit 501 delays the data bit fed-back from thesecond delay unit 503 by a pre-determined time (e.g., by 1 clock). Then,the first delay unit 501 outputs the delayed data bit to the first adder502 and the second adder 504. The second adder 504 adds the data bitsoutputted from the first and second delay units 501 and 503 as a lowerbit u2. The third adder 505 adds the input data bit U and the output ofthe second delay unit 503 and outputs the added data bit as a lower bitu3.

At this point, if the input data bit U corresponds to data encoded at a½-coding rate, the symbol encoder 402 configures a symbol with u1u0 bitsfrom the 4 output bits u0u1u2u3. Then, the symbol encoder 402 outputsthe newly configured symbol. Alternatively, if the input data bit Ucorresponds to data encoded at a ¼-coding rate, the symbol encoder 402configures and outputs a symbol with bits u1u0 and, then, configures andoutputs another symbol with bits u2u3. According to another embodimentof the present invention, if the input data bit U corresponds to dataencoded at a ¼-coding rate, the symbol encoder 402 may also configureand output a symbol with bits u1u0, and then repeat the process onceagain and output the corresponding bits. According to yet anotherembodiment of the present invention, the symbol encoder outputs all fouroutput bits U u0u1u2u3. Then, when using the ½-coding rate, the symbolinterleaver 403 located behind the symbol encoder 402 selects only thesymbol configured of bits u1u0 from the four output bits u0u1u2u3.Alternatively, when using the ¼-coding rate, the symbol interleaver 403may select the symbol configured of bits u1u0 and then select anothersymbol configured of bits u2u3. According to another embodiment, whenusing the ¼-coding rate, the symbol interleaver 403 may repeatedlyselect the symbol configured of bits u1u0.

The output of the symbol encoder 402 is inputted to the symbolinterleaver 403. Then, the symbol interleaver 403 performs blockinterleaving in symbol units on the data outputted from the symbolencoder 402. Any interleaver performing structural rearrangement (orrealignment) may be applied as the symbol interleaver 403 of the blockprocessor. However, in the present invention, a variable length symbolinterleaver that can be applied even when a plurality of lengths isprovided for the symbol, so that its order may be rearranged, may alsobe used.

FIG. 11 illustrates a symbol interleaver according to an embodiment ofthe present invention. Herein, the symbol interleaver according to theembodiment of the present invention corresponds to a variable lengthsymbol interleaver that may be applied even when a plurality of lengthsis provided for the symbol, so that its order may be rearranged.Particularly, FIG. 11 illustrates an example of the symbol interleaverwhen K=6 and L=8. Herein, K indicates a number of symbols that areoutputted for symbol interleaving from the symbol encoder 402. And, Lrepresents a number of symbols that are actually interleaved by thesymbol interleaver 403.

In the present invention, the symbol interleaver 403 should satisfy theconditions of L=2^(n) (wherein n is an integer) and of L≧K. If there isa difference in value between K and L, (L−K) number of null (or dummy)symbols is added, thereby creating an interleaving pattern. Therefore, Kbecomes a block size of the actual symbols that are inputted to thesymbol interleaver 403 in order to be interleaved. L becomes aninterleaving unit when the interleaving process is performed by aninterleaving pattern created from the symbol interleaver 403. Theexample of what is described above is illustrated in FIG. 11.

More specifically, FIG. 11( a) to FIG. 11( c) illustrate a variablelength interleaving process of a symbol interleaver shown in FIG. 9. Thenumber of symbols outputted from the symbol encoder 402 in order to beinterleaved is equal to 6 (i.e., K=6). In other words, 6 symbols areoutputted from the symbol encoder 402 in order to be interleaved. And,the actual interleaving unit (L) is equal to 8 symbols. Therefore, asshown in FIG. 11( a), 2 symbols are added to the null (or dummy) symbol,thereby creating the interleaving pattern. Equation 2 shown belowdescribed the process of sequentially receiving K number of symbols, theorder of which is to be rearranged, and obtaining an L value satisfyingthe conditions of L=2^(n) (wherein n is an integer) and of L≧K, therebycreating the interleaving so as to realign (or rearrange) the symbolorder.

In relation to all places, wherein 0≦i≦L−1,P(i)={S×i×(i+1)/2} mod L  Equation 2

Herein, L≧K, L=2^(n), and n and S are integers. Referring to FIG. 11, itis assumed that S is equal to 89, and that L is equal to 8, and FIG. 11illustrates the created interleaving pattern and an example of theinterleaving process. As shown in FIG. 11( b), the order of K number ofinput symbols and (L−K) number of null symbols is rearranged by usingthe above-mentioned Equation 2. Then, as shown in FIG. 11( c), the nullbyte places are removed, so as to rearrange the order, by using Equation3 shown below. Thereafter, the symbol that is interleaved by therearranged order is then outputted to the symbol-byte converter.if P(i)>K−1, then P(i) place is removed and rearranged  Equation 3

Subsequently, the symbol-byte converter 404 converts to bytes the mobileservice data symbols, having the rearranging of the symbol ordercompleted and then outputted in accordance with the rearranged order,and thereafter outputs the converted bytes to the group formatter 304.

FIG. 12A illustrates a block diagram showing the structure of a blockprocessor according to another embodiment of the present invention.Herein, the block processor includes an interleaving unit 610 and ablock formatter 620. The interleaving unit 610 may include a byte-symbolconverter 611, a symbol-byte converter 612, a symbol interleaver 613,and a symbol-byte converter 614. Herein, the symbol interleaver 613 mayalso be referred to as a block interleaver.

The byte-symbol converter 611 of the interleaving unit 610 converts themobile service data X outputted in byte units from the RS frame encoder302 to symbol units. Then, the byte-symbol converter 611 outputs theconverted mobile service data symbols to the symbol-byte converter 612and the symbol interleaver 613. More specifically, the byte-symbolconverter 611 converts each 2 bits of the inputted mobile service databyte (=8 bits) to 1 symbol and outputs the converted symbols. This isbecause the input data of the trellis encoding module 256 consist ofsymbol units configured of 2 bits. The relationship between the blockprocessor 303 and the trellis encoding module 256 will be described indetail in a later process. At this point, the byte-symbol converter 611may also receive signaling information including transmissionparameters. Furthermore, the signaling information bytes may also bedivided into symbol units and then outputted to the symbol-byteconverter 612 and the symbol interleaver 613.

The symbol-byte converter 612 groups 4 symbols outputted from thebyte-symbol converter 611 so as to configure a byte. Thereafter, theconverted data bytes are outputted to the block formatter 620. Herein,each of the symbol-byte converter 612 and the byte-symbol converter 611respectively performs an inverse process on one another. Therefore, theyield of these two blocks is offset. Accordingly, as shown in FIG. 12B,the input data X bypass the byte-symbol converter 611 and thesymbol-byte converter 612 and are directly inputted to the blockformatter 620. More specifically, the interleaving unit 610 of FIG. 12Bhas a structure equivalent to that of the interleaving unit shown inFIG. 12A. Therefore, the same reference numerals will be used in FIG.12A and FIG. 12B.

The symbol interleaver 613 performs block interleaving in symbol unitson the data that are outputted from the byte-symbol converter 611.Subsequently, the symbol interleaver 613 outputs the interleaved data tothe symbol-byte converter 614. Herein, any type of interleaver that canrearrange the structural order may be used as the symbol interleaver 613of the present invention. In the example given in the present invention,a variable length interleaver that may be applied for symbols having awide range of lengths, the order of which is to be rearranged. Forexample, the symbol interleaver of FIG. 11 may also be used in the blockprocessor shown in FIG. 12A and FIG. 12B.

The symbol-byte converter 614 outputs the symbols having the rearrangingof the symbol order completed, in accordance with the rearranged order.Thereafter, the symbols are grouped to be configured in byte units,which are then outputted to the block formatter 620. More specifically,the symbol-byte converter 614 groups 4 symbols outputted from the symbolinterleaver 613 so as to configure a data byte. As shown in FIG. 13, theblock formatter 620 performs the process of aligning the output of eachsymbol-byte converter 612 and 614 within the block in accordance with aset standard. Herein, the block formatter 620 operates in associationwith the trellis encoding module 256.

More specifically, the block formatter 620 decides the output order ofthe mobile service data outputted from each symbol-byte converter 612and 614 while taking into consideration the place (or order) of the dataexcluding the mobile service data that are being inputted, wherein themobile service data include main service data, known data, RS paritydata, and MPEG header data.

According to the embodiment of the present invention, the trellisencoding module 256 is provided with 12 trellis encoders. FIG. 14illustrates a block diagram showing the trellis encoding module 256according to the present invention. In the example shown in FIG. 14, 12identical trellis encoders are combined to the interleaver in order todisperse noise. Herein, each trellis encoder may be provided with apre-coder.

FIG. 15A illustrates the block processor 303 being concatenated with thetrellis encoding module 256. In the transmitting system, a plurality ofblocks actually exists between the pre-processor 230 including the blockprocessor 303 and the trellis encoding module 256, as shown in FIG. 3.Conversely, the receiving system considers the pre-processor 230 to beconcatenated with the trellis encoding module 256, thereby performingthe decoding process accordingly. However, the data excluding the mobileservice data that are being inputted to the trellis encoding module 256,wherein the mobile service data include main service data, known data,RS parity data, and MPEG header data, correspond to data that are addedto the blocks existing between the block processor 303 and the trellisencoding module 256. FIG. 15B illustrates an example of a data processor650 being positioned between the block processor 303 and the trellisencoding module 256, while taking the above-described instance intoconsideration.

Herein, when the interleaving unit 610 of the block processor 303performs a ½-rate encoding process, the interleaving unit 610 may beconfigured as shown in FIG. 12A (or FIG. 12B). Referring to FIG. 3, forexample, the data processor 650 may include a group formatter 304, adata deinterleaver 305, a packet formatter 306, a packet multiplexer240, and a post-processor 250, wherein the post-processor 250 includes adata randomizer 251, a RS encoder/non-systematic RS encoder 252, a datainterleaver 253, a parity replacer 254, and a non-systematic RS encoder255.

At this point, the trellis encoding module 256 symbolizes the data thatare being inputted so as to divide the symbolized data and to send thedivided data to each trellis encoder in accordance with a pre-definedmethod. Herein, one byte is converted into 4 symbols, each beingconfigured of 2 bits. Also, the symbols created from the single databyte are all transmitted to the same trellis encoder. Accordingly, eachtrellis encoder pre-codes an upper bit of the input symbol, which isthen outputted as the uppermost output bit C2. Alternatively, eachtrellis encoder trellis-encodes a lower bit of the input symbol, whichis then outputted as two output bits C1 and C0. The block formatter 620is controlled so that the data byte outputted from each symbol-byteconverter can be transmitted to different trellis encoders.

Hereinafter, the operation of the block formatter 620 will now bedescribed in detail with reference to FIG. 9 to FIG. 12. Referring toFIG. 12A, for example, the data byte outputted from the symbol-byteconverter 612 and the data byte outputted from the symbol-byte converter614 are inputted to different trellis encoders of the trellis encodingmodule 256 in accordance with the control of the block formatter 620.Hereinafter, the data byte outputted from the symbol-byte converter 612will be referred to as X, and the data byte outputted from thesymbol-byte converter 614 will be referred to as Y, for simplicity.Referring to FIG. 13( a), each number (i.e., 0 to 11) indicates thefirst to twelfth trellis encoders of the trellis encoding module 256,respectively.

In addition, the output order of both symbol-byte converters arearranged (or aligned) so that the data bytes outputted from thesymbol-byte converter 612 are respectively inputted to the 0^(th) to5^(th) trellis encoders (0 to 5) of the trellis encoding module 256, andthat the data bytes outputted from the symbol-byte converter 614 arerespectively inputted to the 6^(th) to 11^(th) trellis encoders (6 to11) of the trellis encoding module 256. Herein, the trellis encodershaving the data bytes outputted from the symbol-byte converter 612allocated therein, and the trellis encoders having the data bytesoutputted from the symbol-byte converter 614 allocated therein aremerely examples given to simplify the understanding of the presentinvention. Furthermore, according to an embodiment of the presentinvention, and assuming that the input data of the block processor 303correspond to a block configured of 12 bytes, the symbol-byte converter612 outputs 12 data bytes from X0 to X11, and the symbol-byte converter614 outputs 12 data bytes from Y0 to Y11.

FIG. 13( b) illustrates an example of data being inputted to the trellisencoding module 256. Particularly, FIG. 13( b) illustrates an example ofnot only the mobile service data but also the main service data and RSparity data being inputted to the trellis encoding module 256, so as tobe distributed to each trellis encoder. More specifically, the mobileservice data outputted from the block processor 303 pass through thegroup formatter 304, from which the mobile service data are mixed withthe main service data and RS parity data and then outputted, as shown inFIG. 13( a). Accordingly, each data byte is respectively inputted to the12 trellis encoders in accordance with the positions (or places) withinthe data group after being data-interleaved.

Herein, when the output data bytes X and Y of the symbol-byte converters612 and 614 are allocated to each respective trellis encoder, the inputof each trellis encoder may be configured as shown in FIG. 13( b). Morespecifically, referring to FIG. 13( b), the six mobile service databytes (X0 to X5) outputted from the symbol-byte converter 612 aresequentially allocated (or distributed) to the first to sixth trellisencoders (0 to 5) of the trellis encoding module 256. Also, the 2 mobileservice data bytes Y0 and Y1 outputted from the symbol-byte converter614 are sequentially allocated to the 7^(th) and 8^(th) trellis encoders(6 and 7) of the trellis encoding module 256. Thereafter, among the 5main service data bytes, 4 data bytes are sequentially allocated to the9^(th) and 12^(th) trellis encoders (8 to 11) of the trellis encodingmodule 256. Finally, the remaining 1 byte of the main service data byteis allocated once again to the first trellis encoder (0).

It is assumed that the mobile service data, the main service data, andthe RS parity data are allocated to each trellis encoder, as shown inFIG. 13( b). It is also assumed that, as described above, the input ofthe block processor 303 is configured of 12 bytes, and that 12 bytesfrom X0 to X11 are outputted from the symbol-byte converter 612, andthat 12 bytes from Y0 to Y11 are outputted from the symbol-byteconverter 614. In this case, as shown in FIG. 13( c), the blockformatter 620 arranges the data bytes that are to be outputted from thesymbol-byte converters 612 and 614 by the order of X0 to X5, Y0, Y1, X6to X10, Y2 to Y7, X11, and Y8 to Y11. More specifically, the trellisencoder that is to perform the encoding process is decided based uponthe position (or place) within the transmission frame in which each databyte is inserted. At this point, not only the mobile service data butalso the main service data, the MPEG header data, and the RS parity dataare also inputted to the trellis encoding module 256. Herein, it isassumed that, in order to perform the above-described operation, theblock formatter 620 is informed of (or knows) the information on thedata group format after the data-interleaving process.

FIG. 16 illustrates a block diagram of the block processor performing anencoding process at a coding rate of 1/N according to an embodiment ofthe present invention. Herein, the block processor includes (N−1) numberof symbol interleavers 741 to 74N−1, which are configured in a parallelstructure. More specifically, the block processor having the coding rateof 1/N consists of a total of N number of branches (or paths) includinga branch (or path), which is directly transmitted to the block formatter730. In addition, the symbol interleaver 741 to 74N−1 of each branch mayeach be configured of a different symbol interleaver. Furthermore, (N−1)number of symbol-byte converter 751 to 75N−1 each corresponding to each(N−1) number of symbol interleavers 741 to 74N−1 may be included at theend of each symbol interleaver, respectively. Herein, the output data ofthe (N−1) number of symbol-byte converter 751 to 75N−1 are also inputtedto the block formatter 730.

In the example of the present invention, N is equal to or smaller than12. If N is equal to 12, the block formatter 730 may align the outputdata so that the output byte of the 12^(th) symbol-byte converter 75N−1is inputted to the 12^(th) trellis encoder. Alternatively, if N is equalto 3, the block formatter 730 may arranged the output order, so that thedata bytes outputted from the symbol-byte converter 720 are inputted tothe 1^(st) to 4^(th) trellis encoders of the trellis encoding module256, and that the data bytes outputted from the symbol-byte converter751 are inputted to the 5^(th) to 8^(th) trellis encoders, and that thedata bytes outputted from the symbol-byte converter 752 are inputted tothe 9^(th) to 12^(th) trellis encoders. At this point, the order of thedata bytes outputted from each symbol-byte converter may vary inaccordance with the position within the data group of the data otherthan the mobile service data, which are mixed with the mobile servicedata that are outputted from each symbol-byte converter.

FIG. 17 illustrates a detailed block diagram showing the structure of ablock processor according to another embodiment of the presentinvention. Herein, the block formatter is removed from the blockprocessor so that the operation of the block formatter may be performedby a group formatter. More specifically, the block processor of FIG. 17may include a byte-symbol converter 810, symbol-byte converters 820 and840, and a symbol interleaver 830. In this case, the output of eachsymbol-byte converter 820 and 840 is inputted to the group formatter850.

Also, the block processor may obtain a desired coding rate by addingsymbol interleavers and symbol-byte converters. If the system designerwishes a coding rate of 1/N, the block processor needs to be providedwith a total of N number of branches (or paths) including a branch (orpath), which is directly transmitted to the block formatter 850, and(N−1) number of symbol interleavers and symbol-byte convertersconfigured in a parallel structure with (N−1) number of branches. Atthis point, the group formatter 850 inserts place holders ensuring thepositions (or places) for the MPEG header, the non-systematic RS parity,and the main service data. And, at the same time, the group formatter850 positions the data bytes outputted from each branch of the blockprocessor.

The number of trellis encoders, the number of symbol-byte converters,and the number of symbol interleavers proposed in the present inventionare merely exemplary. And, therefore, the corresponding numbers do notlimit the spirit or scope of the present invention. It is apparent tothose skilled in the art that the type and position of each data bytebeing allocated to each trellis encoder of the trellis encoding module256 may vary in accordance with the data group format. Therefore, thepresent invention should not be understood merely by the examples givenin the description set forth herein. The mobile service data that areencoded at a coding rate of 1/N and outputted from the block processor303 are inputted to the group formatter 304. Herein, in the example ofthe present invention, the order of the output data outputted from theblock formatter of the block processor 303 are aligned and outputted inaccordance with the position of the data bytes within the data group.

Signaling Information Processing

The transmitter 200 according to the present invention may inserttransmission parameters by using a plurality of methods and in aplurality of positions (or places), which are then transmitted to thereceiving system. For simplicity, the definition of a transmissionparameter that is to be transmitted from the transmitter to thereceiving system will now be described. The transmission parameterincludes data group information, region information within a data group,the number of RS frames configuring a super frame (i.e., a super framesize (SFS)), the number of RS parity data bytes (P) for each columnwithin the RS frame, whether or not a checksum, which is added todetermine the presence of an error in a row direction within the RSframe, has been used, the type and size of the checksum if the checksumis used (presently, 2 bytes are added to the CRC), the number of datagroups configuring one RS frame—since the RS frame is transmitted to oneburst section, the number of data groups configuring the one RS frame isidentical to the number of data groups within one burst (i.e., burstsize (BS)), a turbo code mode, and a RS code mode.

Also, the transmission parameter required for receiving a burst includesa burst period—herein, one burst period corresponds to a value obtainedby counting the number of fields starting from the beginning of acurrent burst until the beginning of a next burst, a positioning orderof the RS frames that are currently being transmitted within a superframe (i.e., a permuted frame index (PFI)) or a positioning order ofgroups that are currently being transmitted within a RS frame (burst)(i.e., a group index (GI)), and a burst size. Depending upon the methodof managing a burst, the transmission parameter also includes the numberof fields remaining until the beginning of the next burst (i.e., time tonext burst (TNB)). And, by transmitting such information as thetransmission parameter, each data group being transmitted to thereceiving system may indicate a relative distance (or number of fields)between a current position and the beginning of a next burst.

The information included in the transmission parameter corresponds toexamples given to facilitate the understanding of the present invention.Therefore, the proposed examples do not limit the scope or spirit of thepresent invention and may be easily varied or modified by anyone skilledin the art. According to the first embodiment of the present invention,the transmission parameter may be inserted by allocating a predeterminedregion of the mobile service data packet or the data group. In thiscase, the receiving system performs synchronization and equalization ona received signal, which is then decoded by symbol units. Thereafter,the packet deformatter may separate the mobile service data and thetransmission parameter so as to detect the transmission parameter.According to the first embodiment, the transmission parameter may beinserted from the group formatter 304 and then transmitted.

According to the second embodiment of the present invention, thetransmission parameter may be multiplexed with another type of data. Forexample, when known data are multiplexed with the mobile service data, atransmission parameter may be inserted, instead of the known data, in aplace (or position) where a known data byte is to be inserted.Alternatively, the transmission parameter may be mixed with the knowndata and then inserted in the place where the known data byte is to beinserted. According to the second embodiment, the transmission parametermay be inserted from the group formatter 304 or from the packetformatter 306 and then transmitted.

According to a third embodiment of the present invention, thetransmission parameter may be inserted by allocating a portion of areserved region within a field synchronization segment of a transmissionframe. In this case, since the receiving system may perform decoding ona receiving signal by symbol units before detecting the transmissionparameter, the transmission parameter having information on theprocessing methods of the block processor 303 and the group formatter304 may be inserted in a reserved field of a field synchronizationsignal. More specifically, the receiving system obtains fieldsynchronization by using a field synchronization segment so as to detectthe transmission parameter from a pre-decided position. According to thethird embodiment, the transmission parameter may be inserted from thesynchronization multiplexer 240 and then transmitted.

According to the fourth embodiment of the present invention, thetransmission parameter may be inserted in a layer (or hierarchicalregion) higher than a transport stream (TS) packet. In this case, thereceiving system should be able to receive a signal and process thereceived signal to a layer higher than the TS packet in advance. At thispoint, the transmission parameter may be used to certify thetransmission parameter of a currently received signal and to provide thetransmission parameter of a signal that is to be received in a laterprocess.

In the present invention, the variety of transmission parametersassociated with the transmission signal may be inserted and transmittedby using the above-described methods according to the first to fourthembodiment of the present invention. At this point, the transmissionparameter may be inserted and transmitted by using only one of the fourembodiments described above, or by using a selection of theabove-described embodiments, or by using all of the above-describedembodiments. Furthermore, the information included in the transmissionparameter may be duplicated and inserted in each embodiment.Alternatively, only the required information may be inserted in thecorresponding position of the corresponding embodiment and thentransmitted. Furthermore, in order to ensure robustness of thetransmission parameter, a block encoding process of a short cycle (orperiod) may be performed on the transmission parameter and, then,inserted in a corresponding region. The method for performing ashort-period block encoding process on the transmission parameter mayinclude, for example, Kerdock encoding, BCH encoding, RS encoding, andrepetition encoding of the transmission parameter. Also, a combinationof a plurality of block encoding methods may also be performed on thetransmission parameter.

The transmission parameters may be grouped to create a block code of asmall size, so as to be inserted in a byte place allocated within thedata group for signaling and then transmitted. However, in this case,the block code passes through the block decoded from the receiving endso as to obtain a transmission parameter value. Therefore, thetransmission parameters of the turbo code mode and the RS code mode,which are required for block decoding, should first be obtained.Accordingly, the transmission parameters associated with a particularmode may be inserted in a specific section of a known data region. And,in this case, a correlation of with a symbol may be used for a fasterdecoding process. The receiving system refers to the correlation betweeneach sequence and the currently received sequences, thereby determiningthe encoding mode and the combination mode.

Meanwhile, when the transmission parameter is inserted in the fieldsynchronization segment region or the known data region and thentransmitted, and when the transmission parameter has passed through thetransmission channel, the reliability of the transmission parameter isdeteriorated. Therefore, one of a plurality of pre-defined patterns mayalso be inserted in accordance with the corresponding transmissionparameter. Herein, the receiving system performs a correlationcalculation between the received signal and the pre-defined patterns soas to recognize the transmission parameter. For example, it is assumedthat a burst including 5 data groups is pre-decided as pattern A basedupon an agreement between the transmitting system and the receivingsystem. In this case, the transmitting system inserts and transmitspattern A, when the number of groups within the burst is equal to 5.Thereafter, the receiving system calculates a correlation between thereceived data and a plurality of reference patterns including pattern A,which was created in advance. At this point, if the correlation valuebetween the received data and pattern A is the greatest, the receiveddata indicates the corresponding parameter, and most particularly, thenumber of groups within the burst. At this point, the number of groupsmay be acknowledged as 5. Hereinafter, the process of inserting andtransmitting the transmission parameter will now be described accordingto first, second, and third embodiments of the present invention.

First Embodiment

FIG. 18 illustrates a schematic diagram of the group formatter 304receiving the transmission parameter and inserting the receivedtransmission parameter in region A of the data group according to thepresent invention. Herein, the group formatter 304 receives mobileservice data from the block processor 303. Conversely, the transmissionparameter is processed with at least one of a data randomizing process,a RS frame encoding process, and a block processing process, and maythen be inputted to the group formatter 304. Alternatively, thetransmission parameter may be directly inputted to the group formatter304 without being processed with any of the above-mentioned processes.In addition, the transmission parameter may be provided from the servicemultiplexer 100. Alternatively, the transmission parameter may also begenerated and provided from within the transmitter 200. The transmissionparameter may also include information required by the receiving systemin order to receive and process the data included in the data group. Forexample, the transmission parameter may include data group information,and multiplexing information.

The group formatter 304 inserts the mobile service data and transmissionparameter which are to be inputted to corresponding regions within thedata group in accordance with a rule for configuring a data group. Forexample, the transmission parameter passes through a block encodingprocess of a short period and is, then, inserted in region A of the datagroup. Particularly, the transmission parameter may be inserted in apre-arranged and arbitrary position (or place) within region A. If it isassumed that the transmission parameter has been block encoded by theblock processor 303, the block processor 303 performs the same dataprocessing operation as the mobile service data, more specifically,either a ½-rate encoding or ¼-rate encoding process on the signalinginformation including the transmission parameter. Thereafter, the blockprocessor 303 outputs the processed transmission parameter to the groupformatter 304. Thereafter, the signaling information is also recognizedas the mobile service data and processed accordingly.

FIG. 19 illustrates a block diagram showing an example of the blockprocessor receiving the transmission parameter and processing thereceived transmission parameter with the same process as the mobileservice data. Particularly, FIG. 19 illustrates an example showing thestructure of FIG. 9 further including a signaling information provider411 and multiplexer 412. More specifically, the signaling informationprovider 411 outputs the signaling information including thetransmission parameter to the multiplexer 412. The multiplexer 412multiplexes the signaling information and the output of the RS frameencoder 302. Then, the multiplexer 412 outputs the multiplexed data tothe byte-bit converter 401.

The byte-bit converter 401 divides the mobile service data bytes orsignaling information byte outputted from the multiplexer 412 into bits,which are then outputted to the symbol encoder 402. The subsequentoperations are identical to those described in FIG. 9. Therefore, adetailed description of the same will be omitted for simplicity. If anyof the detailed structures of the block processor 303 shown in FIG. 12,FIG. 15, FIG. 16, and FIG. 17, the signaling information provider 411and the multiplexer 412 may be provided behind the byte-symbolconverter.

Second Embodiment

Meanwhile, when known data generated from the group formatter inaccordance with a pre-decided rule are inserted in a correspondingregion within the data group, a transmission parameter may be insertedin at least a portion of a region, where known data may be inserted,instead of the known data. For example, when a long known data sequenceis inserted at the beginning of region A within the data group, atransmission parameter may be inserted in at least a portion of thebeginning of region A instead of the known data. A portion of the knowndata sequence that is inserted in the remaining portion of region A,excluding the portion in which the transmission parameter is inserted,may be used to detect a starting point of the data group by thereceiving system. Alternatively, another portion of region A may be usedfor channel equalization by the receiving system.

In addition, when the transmission parameter is inserted in the knowndata region instead of the actual known data. The transmission parametermay be block encoded in short periods and then inserted. Also, asdescribed above, the transmission parameter may also be inserted basedupon a pre-defined pattern in accordance with the transmissionparameter. If the group formatter 304 inserts known data place holdersin a region within the data group, wherein known data may be inserted,instead of the actual known data, the transmission parameter may beinserted by the packet formatter 306. More specifically, when the groupformatter 304 inserts the known data place holders, the packet formatter306 may insert the known data instead of the known data place holders.Alternatively, when the group formatter 304 inserts the known data, theknown data may be directly outputted without modification.

FIG. 20 illustrates a block diagram showing the structure of a packetformatter 306 being expanded so that the packet formatter 306 can insertthe transmission parameter according to an embodiment of the presentinvention. More specifically, the structure of the packet formatter 306further includes a known data generator 351 and a signaling multiplexer352. Herein, the transmission parameter that is inputted to thesignaling multiplexer 352 may include information on the length of acurrent burst, information indicating a starting point of a next burst,positions in which the groups within the burst exist and the lengths ofthe groups, information on the time from the current group and the nextgroup within the burst, and information on known data.

The signaling multiplexer 352 selects one of the transmission parameterand the known data generated from the known data generator 351 and,then, outputs the selected data to the packet formatter 306. The packetformatter 306 inserts the known data or transmission parameter outputtedfrom the signaling multiplexer 352 into the known data place holdersoutputted from the data interleaver 305. Then, the packet formatter 306outputs the processed data. More specifically, the packet formatter 306inserts a transmission parameter in at least a portion of the known dataregion instead of the known data, which is then outputted. For example,when a known data place holder is inserted at a beginning portion ofregion A within the data group, a transmission parameter may be insertedin a portion of the known data place holder instead of the actual knowndata.

Also, when the transmission parameter is inserted in the known dataplace holder instead of the known data, the transmission parameter maybe block encoded in short periods and inserted. Alternatively, apre-defined pattern may be inserted in accordance with the transmissionparameter. More specifically, the signaling multiplexer 352 multiplexesthe known data and the transmission parameter (or the pattern defined bythe transmission parameter) so as to configure a new known datasequence. Then, the signaling multiplexer 352 outputs the newlyconfigured known data sequence to the packet formatter 306. The packetformatter 306 deletes the main service data place holder and RS parityplace holder from the output of the data interleaver 305, and creates amobile service data packet of 188 bytes by using the mobile servicedata, MPEG header, and the output of the signaling multiplexer. Then,the packet formatter 306 outputs the newly created mobile service datapacket to the packet multiplexer 240.

In this case, the region A of each data group has a different known datapattern. Therefore, the receiving system separates only the symbol in apre-arranged section of the known data sequence and recognizes theseparated symbol as the transmission parameter. Herein, depending uponthe design of the transmitting system, the known data may be inserted indifferent blocks, such as the packet formatter 306, the group formatter304, or the block processor 303. Therefore, a transmission parameter maybe inserted instead of the known data in the block wherein the knowndata are to be inserted.

According to the second embodiment of the present invention, atransmission parameter including information on the processing method ofthe block processor 303 may be inserted in a portion of the known dataregion and then transmitted. In this case, a symbol processing methodand position of the symbol for the actual transmission parameter symbolare already decided. Also, the position of the transmission parametersymbol should be positioned so as to be transmitted or received earlierthan any other data symbols that are to be decoded. Accordingly, thereceiving system may detect the transmission symbol before the datasymbol decoding process, so as to use the detected transmission symbolfor the decoding process.

Third Embodiment

Meanwhile, the transmission parameter may also be inserted in the fieldsynchronization segment region and then transmitted. FIG. 21 illustratesa block diagram showing the synchronization multiplexer being expandedin order to allow the transmission parameter to be inserted in the fieldsynchronization segment region. Herein, a signaling multiplexer 261 isfurther included in the synchronization multiplexer 260. Thetransmission parameter of the general VSB method is configured of 2fields. More specifically, each field is configured of one fieldsynchronization segment and 312 data segments. Herein, the first 4symbols of a data segment correspond to the segment synchronizationportion, and the first data segment of each field corresponds to thefield synchronization portion.

One field synchronization signal is configured to have the length of onedata segment. The data segment synchronization pattern exists in thefirst 4 symbols, which are then followed by pseudo random sequences PN511, PN 63, PN 63, and PN 63. The next 24 symbols include informationassociated with the VSB mode. Additionally, the 24 symbols that includeinformation associated with the VSB mode are followed by the remaining104 symbols, which are reserved symbols. Herein, the last 12 symbols ofa previous segment are copied and positioned as the last 12 symbols inthe reserved region. In other words, only the 92 symbols in the fieldsynchronization segment are the symbols that correspond to the actualreserved region.

Therefore, the signaling multiplexer 261 multiplexes the transmissionparameter with an already-existing field synchronization segment symbol,so that the transmission parameter can be inserted in the reservedregion of the field synchronization segment. Then, the signalingmultiplexer 261 outputs the multiplexed transmission parameter to thesynchronization multiplexer 260. The synchronization multiplexer 260multiplexes the segment synchronization symbol, the data symbols, andthe new field synchronization segment outputted from the signalingmultiplexer 261, thereby configuring a new transmission frame. Thetransmission frame including the field synchronization segment, whereinthe transmission parameter is inserted, is outputted to the transmissionunit 270. At this point, the reserved region within the fieldsynchronization segment for inserting the transmission parameter maycorrespond to a portion of or the entire 92 symbols of the reservedregion. Herein, the transmission parameter being inserted in thereserved region may, for example, include information identifying thetransmission parameter as the main service data, the mobile servicedata, or a different type of mobile service data.

If the information on the processing method of the block processor 303is transmitted as a portion of the transmission parameter, and when thereceiving system wishes to perform a decoding process corresponding tothe block processor 303, the receiving system should be informed of suchinformation on the block processing method in order to perform thedecoding process. Therefore, the information on the processing method ofthe block processor 303 should already be known prior to the blockdecoding process. Accordingly, as described in the third embodiment ofthe present invention, when the transmission parameter having theinformation on the processing method of the block processor 303 (and/orthe group formatter 304) is inserted in the reserved region of the fieldsynchronization signal and then transmitted, the receiving system iscapable of detecting the transmission parameter prior to performing theblock decoding process on the received signal.

Receiving System

FIG. 22 illustrates a block diagram showing a structure of a digitalbroadcast receiving system according to the present invention. Thedigital broadcast receiving system of FIG. 22 uses known datainformation, which is inserted in the mobile service data section and,then, transmitted by the transmitting system, so as to perform carriersynchronization recovery, frame synchronization recovery, and channelequalization, thereby enhancing the receiving performance. Referring toFIG. 22, the digital broadcast receiving system includes a tuner 901, ademodulator 902, an equalizer 903, a known data detector 904, a blockdecoder 905, a data deformatter 906, a RS frame decoder 907, aderandomizer 908, a data deinterleaver 909, a RS decoder 910, and a dataderandomizer 911. Herein, for simplicity of the description of thepresent invention, the data deformatter 906, the RS frame decoder 907,and the derandomizer 908 will be collectively referred to as a mobileservice data processing unit. And, the data deinterleaver 909, the RSdecoder 910, and the data derandomizer 911 will be collectively referredto as a main service data processing unit.

More specifically, the tuner 901 tunes a frequency of a particularchannel and down-converts the tuned frequency to an intermediatefrequency (IF) signal. Then, the tuner 901 outputs the down-converted IFsignal to the demodulator 902 and the known data detector 904. Thedemodulator 902 performs self gain control, carrier recovery, and timingrecovery processes on the inputted IF signal, thereby modifying the IFsignal to a baseband signal. Herein, an analog/digital converter (ADC)converting pass band analog IF signals to digital IF signals may beincluded between the tuner 901 and the demodulator 902. Then, thedemodulator 902 outputs the digitalized and inputted pass band IF signalto the equalizer 903 and the known data detector 904. The equalizer 903compensates the distortion of the channel included in the demodulatedsignal and then outputs the error-compensated signal to the blockdecoder 905.

At this point, the known data detector 904 detects the known sequenceplace inserted by the transmitting end from the input/output data of thedemodulator 902 (i.e., the data prior to the demodulation process or thedata after the demodulation process). Thereafter, the place information(or position indicator) along with the symbol sequence of the knowndata, which are generated from the detected place, is outputted to thedemodulator 902 and the equalizer 903. Also, the known data detector 904outputs a set of information to the block decoder 905. This set ofinformation is used to allow the block decoder 905 of the receivingsystem to identify the mobile service data that are processed withadditional encoding from the transmitting system and the main servicedata that are not processed with additional encoding. In addition,although the connection status is not shown in FIG. 22, the informationdetected from the known data detector 904 may be used throughout theentire receiving system and may also be used in the data deformatter 906and the RS frame decoder 907.

The demodulator 902 uses the known data (or sequence) position indicatorand the known data symbol sequence during the timing and/or carrierrecovery, thereby enhancing the demodulating performance. Similarly, theequalizer 903 uses the known sequence position indicator and the knowndata symbol sequence so as to enhance the equalizing performance.Moreover, the decoding result of the block decoder 905 may be fed-backto the equalizer 903, thereby enhancing the equalizing performance. Atthis point, the transmitting system may periodically insert and transmitknown data within a transmission frame, as shown in FIG. 6A.

FIG. 23 illustrates an example of known data sequence being periodicallyinserted and transmitted in-between actual data by the transmittingsystem. Referring to FIG. 23, A represent s the number of valid datasymbols, and B represents the number of known data symbols. Therefore, Bnumber of known data symbols are inserted and transmitted at a period of(A+B) symbols. Herein, A may correspond to mobile service data, mainservice data, or a combination of mobile service data and main servicedata. In order to be differentiated from the known data, datacorresponding to A will hereinafter be referred to as valid data.

Referring to FIG. 23, known data sequence having the same pattern areincluded in each known data section that is being periodically inserted.Herein, the length of the known data sequence having identical datapatterns may be either equal to or different from the length of theentire (or total) known data sequence of the corresponding known datasection (or block). If the two lengths are different from one another,the length of the entire known data sequence should be longer than thelength of the known data sequence having identical data patterns. Inthis case, the same known data sequences are included in the entireknown data sequence. The known data detector 904 detects the position ofthe known data being periodically inserted and transmitted as describedabove. At the same time, the known data detector 904 may also estimateinitial frequency offset during the process of detecting known data. Inthis case, the demodulator 902 may estimate with more accuracy carrierfrequency offset from the information on the known data position (orknown sequence position indicator) and initial frequency offsetestimation value, thereby compensating the estimated initial frequencyoffset.

FIG. 24 illustrates a detailed block diagram of a demodulator accordingto the present invention. Referring to FIG. 24, the demodulator includesa phase splitter 1010, a numerically controlled oscillator (NCO) 1020, afirst multiplier 1030, a resampler 1040, a second multiplier 1050, amatched filter 1060, a DC remover 1070, a timing recovery unit 1080, acarrier recovery unit 1090, and a phase compensator 1110. Herein, theknown data detector 904 includes a known data detector and initialfrequency offset estimator 9041 for estimating known data informationand initial frequency offset. Also referring to FIG. 24, the phasesplitter 1010 receives a pass band digital signal and splits thereceived signal into a pass band digital signal of a real number elementand a pass band digital signal of an imaginary number element bothhaving a phase of 90 degrees between one another. In other words, thepass band digital signal is split into complex signals. The splitportions of the pass band digital signal are then outputted to the firstmultiplier 1030. Herein, the real number signal outputted from the phasesplitter 1010 will be referred to as an T signal, and the imaginarynumber signal outputted from the phase splitter 1010 will be referred toas a ‘Q’ signal, for simplicity of the description of the presentinvention.

The first multiplier 1030 multiplies the I and Q pass band digitalsignals, which are outputted from the phase splitter 1010, to a complexsignal having a frequency proportional to a constant being outputtedfrom the NCO 1020, thereby changing the I and Q pass band digitalsignals to baseband digital complex signals. Then, the baseband digitalsignals of the first multiplier 1030 are inputted to the resampler 1040.The resampler 1040 resamples the signals being outputted from the firstmultiplier 1030 so that the signal corresponds to the timing clockprovided by the timing recovery unit 1080. Thereafter, the resampler1040 outputs the resampled signals to the second multiplier 1050.

For example, when the analog/digital converter uses a 25 MHz fixedoscillator, the baseband digital signal having a frequency of 25 MHz,which is created by passing through the analog/digital converter, thephase splitter 1010, and the first multiplier 1030, is processed with aninterpolation process by the resampler 1040. Thus, the interpolatedsignal is recovered to a baseband digital signal having a frequencytwice that of the receiving signal of a symbol clock (i.e., a frequencyof 21.524476 MHz). Alternatively, if the analog/digital converter usesthe timing clock of the timing recovery unit 1080 as the samplingfrequency (i.e., if the analog/digital converter uses a variablefrequency) in order to perform an A/D conversion process, the resampler1040 is not required and may be omitted.

The second multiplier 1050 multiplies an output frequency of the carrierrecovery unit 1090 with the output of the resampler 1040 so as tocompensate any remaining carrier included in the output signal of theresampler 1040. Thereafter, the compensated carrier is outputted to thematched filter 1060 and the timing recovery unit 1080. The signalmatched-filtered by the matched filter 1060 is inputted to the DCremover 1070, the known data detector and initial frequency offsetestimator 9041, and the carrier recovery unit 1090.

The known data detector and initial frequency offset estimator 9041detects the place (or position) of the known data sequences that arebeing periodically or non-periodically transmitted. Simultaneously, theknown data detector and initial frequency offset estimator 9041estimates an initial frequency offset during the known data detectionprocess. More specifically, while the transmission data frame is beingreceived, as shown in FIG. 6A, the known data detector and initialfrequency offset estimator 9041 detects the position (or place) of theknown data included in the transmission data frame. Then, the known datadetector and initial frequency offset estimator 9041 outputs thedetected information on the known data place (i.e., a known sequenceposition indicator) to the timing recovery unit 1080, the carrierrecovery unit 1090, and the phase compensator 1110 of the demodulator902 and the equalizer 903. Furthermore, the known data detector andinitial frequency offset estimator 9041 estimates the initial frequencyoffset, which is then outputted to the carrier recovery unit 1090. Atthis point, the known data detector and initial frequency offsetestimator 9041 may either receive the output of the matched filter 1060or receive the output of the resampler 1040. This may be optionallydecided depending upon the design of the system designer.

The timing recovery unit 1080 uses the output of the second multiplier1050 and the known sequence position indicator detected from the knowndata detector and initial frequency offset estimator 9041, so as todetect the timing error and, then, to output a sampling clock being inproportion with the detected timing error to the resampler 1040, therebyadjusting the sampling timing of the resampler 1040. At this point, thetiming recovery unit 1080 may receive the output of the matched filter1060 instead of the output of the second multiplier 1050. This may alsobe optionally decided depending upon the design of the system designer.

Meanwhile, the DC remover 1070 removes a pilot tone signal (i.e., DCsignal), which has been inserted by the transmitting system, from thematched-filtered signal. Thereafter, the DC remover 1070 outputs theprocessed signal to the phase compensator 1110. The phase compensator1110 uses the data having the DC removed by the DC remover 1070 and theknown sequence position indicator detected by the known data detectorand initial frequency offset estimator 9041 to estimate the frequencyoffset and, then, to compensate the phase change included in the outputof the DC remover 1070. The data having its phase change compensated areinputted to the equalizer 903. Herein, the phase compensator 1110 isoptional. If the phase compensator 1110 is not provided, then the outputof the DC remover 1070 is inputted to the equalizer 903 instead.

FIG. 25 includes detailed block diagrams of the timing recovery unit1080, the carrier recovery unit 1090, and the phase compensator 1110 ofthe demodulator. According to an embodiment of the present invention,the carrier recovery unit 1090 includes a buffer 1091, a frequencyoffset estimator 1092, a loop filter 1093, a holder 1094, an adder 1095,and a NCO 1096. Herein, a decimator may be included before the buffer1091. The timing recovery unit 1080 includes a decimator 1081, a buffer1082, a timing error detector 1083, a loop filter 1084, a holder 1085,and a NCO 1086. Finally, the phase compensator 1110 includes a buffer1111, a frequency offset estimator 1112, a holder 1113, a NCO 1114, anda multiplier 1115. Furthermore, a decimator 1500 may be included betweenthe phase compensator 1110 and the equalizer 903. The decimator 1500 maybe outputted in front of the DC remover 1070 instead of at theoutputting end of the phase compensator 1110.

Herein, the decimators correspond to components required when a signalbeing inputted to the demodulator is oversampled to N times by theanalog/digital converter. More specifically, the integer N representsthe sampling rate of the received signal. For example, when the inputsignal is oversampled to 2 times (i.e., when N=2) by the analog/digitalconverter, this indicates that two samples are included in one symbol.In this case, each of the decimators corresponds to a ½ decimator.Depending upon whether or not the oversampling process of the receivedsignal has been performed, the signal may bypass the decimators.

Meanwhile, the output of the second multiplier 1050 is temporarilystored in the decimator 1081 and the buffer 1082 both included in thetiming recovery unit 1080. Subsequently, the temporarily stored outputdata are inputted to the timing error detector 1083 through thedecimator 1081 and the buffer 1082. Assuming that the output of thesecond multiplier 1050 is oversampled to N times its initial state, thedecimator 1081 decimates the output of the second multiplier 1050 at adecimation rate of 1/N. Then, the 1/N-decimated data are inputted to thebuffer 1082. In other words, the decimator 1081 performs decimation onthe input signal in accordance with a VSB symbol cycle. Furthermore, thedecimator 1081 may also receive the output of the matched filter 1060instead of the output of the second multiplier 1050. The timing errordetector 1083 uses the data prior to or after being processed withmatched-filtering and the known sequence position indicator outputtedfrom the known data detector and initial frequency offset estimator 9041in order to detect a timing error. Thereafter, the detected timing erroris outputted to the loop filter 1084. Accordingly, the detected timingerror information is obtained once during each repetition cycle of theknown data sequence.

For example, if a known data sequence having the same pattern isperiodically inserted and transmitted, as shown in FIG. 23, the timingerror detector 1083 may use the known data in order to detect the timingerror. There exists a plurality of methods for detecting timing error byusing the known data. In the example of the present invention, thetiming error may be detected by using a correlation characteristicbetween the known data and the received data in the time domain, theknown data being already known in accordance with a pre-arrangedagreement between the transmitting system and the receiving system. Thetiming error may also be detected by using the correlationcharacteristic of the two known data types being received in thefrequency domain. Thus, the detected timing error is outputted. Inanother example, a spectral lining method may be applied in order todetect the timing error. Herein, the spectral lining method correspondsto a method of detecting timing error by using sidebands of the spectrumincluded in the received signal.

The loop filter 1084 filters the timing error detected by the timingerror detector 1083 and, then, outputs the filtered timing error to theholder 1085. The holder 1085 holds (or maintains) the timing errorfiltered and outputted from the loop filter 1084 during a pre-determinedknown data sequence cycle period and outputs the processed timing errorto the NCO 1086. Herein, the order of positioning of the loop filter1084 and the holder 1085 may be switched with one another. Inadditionally, the function of the holder 1085 may be included in theloop filter 1084, and, accordingly, the holder 1085 may be omitted. TheNCO 1086 accumulates the timing error outputted from the holder 1085.Thereafter, the NCO 1086 outputs the phase element (i.e., a samplingclock) of the accumulated timing error to the resampler 1040, therebyadjusting the sampling timing of the resampler 1040.

Meanwhile, the buffer 1091 of the carrier recovery unit 1090 may receiveeither the data inputted to the matched filter 1060 or the dataoutputted from the matched filter 1060 and, then, temporarily store thereceived data. Thereafter, the temporarily stored data are outputted tothe frequency offset estimator 1092. If a decimator is provided in frontof the buffer 1091, the input data or output data of the matched filter1060 are decimated by the decimator at a decimation rate of 1/N.Thereafter, the decimated data are outputted to the buffer 1091. Forexample, when the input data or output data of the matched filter 1060are oversampled to 2 times (i.e., when N=2), this indicates that theinput data or output data of the matched filter 1060 are decimated at arate of ½ by the decimator 1081 and then outputted to the buffer 1091.More specifically, when a decimator is provided in front of the buffer1091, the carrier recovery unit 1090 operates in symbol units.Alternatively, if a decimator is not provided, the carrier recovery unit1090 operates in oversampling units.

The frequency offset estimator 1092 uses the input data or output dataof the matched filter 1060 and the known sequence position indicatoroutputted from the known data detector and initial frequency offsetestimator 9041 in order to estimate the frequency offset. Then, theestimated frequency offset is outputted to the loop filter 1093.Therefore, the estimated frequency offset value is obtained once everyrepetition period of the known data sequence. The loop filter 1093performs low pass filtering on the frequency offset value estimated bythe frequency offset estimator 1092 and outputs the low pass-filteredfrequency offset value to the holder 1094. The holder 1094 holds (ormaintains) the low pass-filtered frequency offset value during apre-determined known data sequence cycle period and outputs thefrequency offset value to the adder 1095. Herein, the positions of theloop filter 1093 and the holder 1094 may be switched from one to theother. Furthermore, the function of the holder 1085 may be included inthe loop filter 1093, and, accordingly, the holder 1094 may be omitted.

The adder 1095 adds the value of the initial frequency offset estimatedby the known data detector and initial frequency offset estimator 9041to the frequency offset value outputted from the loop filter 1093 (orthe holder 1094). Thereafter, the added offset value is outputted to theNCO 1096. Herein, if the adder 1095 is designed to also receive theconstant being inputted to the NCO 1020, the NCO 1020 and the firstmultiplier 1030 may be omitted. In this case, the second multiplier 1050may simultaneously perform changing signals to baseband signals andremoving remaining carrier.

The NCO 1096 generates a complex signal corresponding to the frequencyoffset outputted from the adder 1095, which is then outputted to thesecond multiplier 1050. Herein, the NCO 1096 may include a ROM. In thiscase, the NCO 1096 generates a compensation frequency corresponding tothe frequency offset being outputted from the adder 1095. Then, the NCO1096 reads a complex cosine corresponding to the compensation frequencyfrom the ROM, which is then outputted to the second multiplier 1050. Thesecond multiplier 1050 multiplies the output of the NCO 1094 included inthe carrier recovery unit 1090 to the output of the resampler 1040, soas to remove the carrier offset included in the output signal of theresampler 1040.

FIG. 26 illustrates a detailed block diagram of the frequency offsetestimator 1092 of the carrier recovery unit 1090 according to anembodiment of the present invention. Herein, the frequency offsetestimator 1092 operates in accordance with the known sequence positionindicator detected from the known data detector and initial frequencyoffset estimator 9041. At this point, if the input data or output dataof the matched filter 1060 are inputted through the decimator, thefrequency offset estimator 1092 operates in symbol units. Alternatively,if a decimator is not provided, the frequency offset estimator 1092operates in oversampling units. In the example given in the descriptionof the present invention, the frequency offset estimator 1092 operatesin symbol units. Referring to FIG. 26, the frequency offset estimator1092 includes a controller 2010, a first N symbol buffer 2011, a Ksymbol delay 2012, a second N symbol buffer 2013, a conjugator 2014, amultiplier 2015, an accumulator 2016, a phase detector 2017, amultiplier 2018, and a multiplexer 2019. The frequency offset estimator1092 having the above-described structure, as shown in FIG. 26, will nowbe described in detail with respect to an operation example during aknown data section.

The first N symbol buffer 2011 may store a maximum of N number of symbolbeing inputted thereto. The symbol data that are temporarily stored inthe first N symbol buffer 2011 are then inputted to the multiplier 2015.At the same time, the inputted symbol is inputted to the K symbol delay2012 so as to be delayed by K symbols. Thereafter, the delayed symbolpasses through the second N symbol buffer 2013 so as to be conjugated bythe conjugator 2014. Thereafter, the conjugated symbol is inputted tothe multiplier 2015. The multiplier 2015 multiplies the output of thefirst N symbol buffer 2011 and the output of the conjugator 2014. Then,the multiplier 2015 outputs the multiplied result to the accumulator2016. Subsequently, the accumulator 2016 accumulates the output of themultiplier 2015 during N symbol periods, thereby outputted theaccumulated result to the phase detector 2017.

The phase detector 2017 extracts the corresponding phase informationfrom the output of the accumulator 2016, which is then outputted to themultiplier 2018. The multiplier 2018 then divides the phase informationby K, thereby outputting the divided result to the multiplexer 2019.Herein, the result of the phase information divided by becomes thefrequency offset estimation value. More specifically, at the point wherethe input of the known data ends or at a desired point, the frequencyoffset estimator 1092 accumulates during an N symbol periodmultiplication of the complex conjugate of N number of the input datastored in the first N symbol buffer 2011 and the complex conjugate ofthe N number of the input data that are delayed by K symbols and storedin the second N symbol buffer 2013. Thereafter, the accumulated value isdivided by K, thereby extracting the frequency offset estimation value.

Based upon a control signal of the controller 2010, the multiplexer 2019selects either the output of the multiplier 2018 or ‘0’ and, then,outputs the selected result as the final frequency offset estimationvalue. The controller 2010 receives the known data sequence positionindicator from the known data detector and initial frequency offsetestimator 9041 in order to control the output of the multiplexer 2019.More specifically, the controller 2010 determines based upon the knowndata sequence position indicator whether the frequency offset estimationvalue being outputted from the multiplier 2018 is valid. If thecontroller 2010 determines that the frequency offset estimation value isvalid, the multiplexer 2019 selects the output of the multiplier 2018.Alternatively, if the controller 2010 determines that the frequencyoffset estimation value is invalid, the controller 2010 generates acontrol signal so that the multiplexer 2019 selects ‘0’. At this point,it is preferable that the input signals stored in the first N symbolbuffer 2011 and in the second N symbol buffer 2013 correspond to signalseach being transmitted by the same known data and passing through almostthe same channel. Otherwise, due to the influence of the transmissionchannel, the frequency offset estimating performance may be largelydeteriorated.

Further, the values N and K of the frequency offset estimator 1092(shown in FIG. 26) may be diversely decided. This is because aparticular portion of the known data that are identically repeated maybe used herein. For example, when the data having the structuredescribed in FIG. 23 are being transmitted, N may be set as B (i.e.,N=B), and K may be set as (A+B) (i.e., K=A+B)). The frequency offsetestimation value range of the frequency offset estimator 1092 is decidedin accordance with the value K. If the value K is large, then thefrequency offset estimation value range becomes smaller. Alternatively,if the value K is small, then the frequency offset estimation valuerange becomes larger. Therefore, when the data having the structure ofFIG. 23 is transmitted, and if the repetition cycle (A+B) of the knowndata is long, then the frequency offset estimation value range becomessmaller.

In this case, even if the initial frequency offset is estimated by theknown sequence detector and initial frequency offset estimator 9041, andif the estimated value is compensated by the second multiplier 1050, theremaining frequency offset after being compensated will exceed theestimation range of the frequency offset estimator 1092. In order toovercome such problems, the known data sequence that is regularlytransmitted may be configured of a repetition of a same data portion byusing a cyclic extension process. For example, if the known datasequence shown in FIG. 23 is configured of two identical portions havingthe length of B/2, then the N and K values of the frequency offsetestimator 1092 (shown in FIG. 26) may be respectively set as B/2 and B/2(i.e., N=B/2 and K=B/2). In this case, the estimation value range maybecome larger than when using repeated known data.

Meanwhile, the known data detector and initial frequency offsetestimator 9041 detects the place (o position) of the known datasequences that are being periodically or non-periodically transmitted.Simultaneously, the known data detector and initial frequency offsetestimator 9041 estimates an initial frequency offset during the knowndata detection process. The known data sequence position indicatordetected by the known data detector and initial frequency offsetestimator 9041 is outputted to the timing recovery unit 1080, thecarrier recovery unit 1090, and the phase compensator 1110 of thedemodulator 902, and to the equalizer 903. Thereafter, the estimatedinitial frequency offset is outputted to the carrier recovery unit 1090.At this point, the known data detector and initial frequency offsetestimator 9041 may either receive the output of the matched filter 1060or receive the output of the resampler 1040. This may be optionallydecided depending upon the design of the system designer. Herein, thefrequency offset estimator shown in FIG. 26 may be directly applied inthe known data detector and initial frequency offset estimator 9041 orin the phase compensator 1110 of the frequency offset estimator.

FIG. 27 illustrates a detailed block diagram showing a known datadetector and initial frequency offset estimator according to anembodiment of the present invention. More specifically, FIG. 27illustrates an example of an initial frequency offset being estimatedalong with the known sequence position indicator. Herein, FIG. 27 showsan example of an inputted signal being oversampled to N times of itsinitial state. In other words, N represents the sampling rate of areceived signal. Referring to FIG. 27, the known data detector andinitial frequency offset estimator includes N number of partialcorrelators 3011 to 301N configured in parallel, a known data placedetector and frequency offset decider 3020, a known data extractor 3030,a buffer 3040, a multiplier 3050, a NCO 3060, a frequency offsetestimator 3070, and an adder 3080. Herein, the first partial correlator3011 consists of a 1/N decimator, and a partial correlator. The secondpartial correlator 3012 consists of a 1 sample delay, a 1/N decimator,and a partial correlator. And, the N^(th) partial correlator 301Nconsists of a N−1 sample delay, a 1/N decimator, and a partialcorrelator. These are used to match (or identify) the phase of each ofthe samples within the oversampled symbol with the phase of the original(or initial) symbol, and to decimate the samples of the remainingphases, thereby performing partial correlation on each sample. Morespecifically, the input signal is decimated at a rate of 1/N for eachsampling phase, so as to pass through each partial correlator.

For example, when the input signal is oversampled to 2 times (i.e., whenN=2), this indicates that two samples are included in one signal. Inthis case, two partial correlators (e.g., 3011 and 3012) are required,and each 1/N decimator becomes a ½ decimator. At this point, the 1/Ndecimator of the first partial correlator 3011 decimates (or removes),among the input samples, the samples located in-between symbol places(or positions). Then, the corresponding 1/N decimator outputs thedecimated sample to the partial correlator. Furthermore, the 1 sampledelay of the second partial correlator 3012 delays the input sample by 1sample (i.e., performs a 1 sample delay on the input sample) and outputsthe delayed input sample to the 1/N decimator. Subsequently, among thesamples inputted from the 1 sample delay, the 1/N decimator of thesecond partial correlator 3012 decimates (or removes) the sampleslocated in-between symbol places (or positions). Thereafter, thecorresponding 1/N decimator outputs the decimated sample to the partialcorrelator.

After each predetermined period of the VSB symbol, each of the partialcorrelators outputs a correlation value and an estimation value of thecoarse frequency offset estimated at that particular moment to the knowndata place detector and frequency offset decider 3020. The known dataplace detector and frequency offset decider 3020 stores the output ofthe partial correlators corresponding to each sampling phase during adata group cycle or a pre-decided cycle. Thereafter, the known dataplace detector and frequency offset decider 3020 decides a position (orplace) corresponding to the highest correlation value, among the storedvalues, as the place (or position) for receiving the known data.Simultaneously, the known data place detector and frequency offsetdecider 3020 finally decides the estimation value of the frequencyoffset estimated at the moment corresponding to the highest correlationvalue as the coarse frequency offset value of the receiving system. Atthis point, the known sequence position indicator is inputted to theknown data extractor 3030, the timing recovery unit 1080, the carrierrecovery unit 1090, the phase compensator 1110, and the equalizer 903,and the coarse frequency offset is inputted to the adder 3080 and theNCO 3060.

In the meantime, while the N number of partial correlators 3011 to 301Ndetect the known data place (or known sequence position) and estimatethe coarse frequency offset, the buffer 3040 temporarily stores thereceived data and outputs the temporarily stored data to the known dataextractor 3030. The known data extractor 3030 uses the known sequenceposition indicator, which is outputted from the known data placedetector and frequency offset decider 3020, so as to extract the knowndata from the output of the buffer 3040. Thereafter, the known dataextractor 3030 outputs the extracted data to the multiplier 3050. TheNCO 3060 generates a complex signal corresponding to the coarsefrequency offset being outputted from the known data place detector andfrequency offset decider 3020. Then, the NCO 3060 outputs the generatedcomplex signal to the multiplier 3050.

The multiplier 3050 multiplies the complex signal of the NCO 3060 to theknown data being outputted from the known data extractor 3030, therebyoutputting the known data having the coarse frequency offset compensatedto the frequency offset estimator 3070. The frequency offset estimator3070 estimates a fine frequency offset from the known data having thecoarse frequency offset compensated. Subsequently, the frequency offsetestimator 3070 outputs the estimated fine frequency offset to the adder3080. The adder 3080 adds the coarse frequency offset to the finefrequency offset. Thereafter, the adder 3080 decides the added result asa final initial frequency offset, which is then outputted to the adder1095 of the carrier recovery unit 1090 included in the demodulator 902.More specifically, during the process of acquiring initialsynchronization, the present invention may estimate and use the coarsefrequency offset as well as the fine frequency offset, thereby enhancingthe estimation performance of the initial frequency offset.

It is assumed that the known data is inserted within the data group andthen transmitted, as shown in FIG. 6A. Then, the known data detector andinitial frequency offset estimator 9041 may use the known data that havebeen additionally inserted between the A1 area and the A2 area, so as toestimate the initial frequency offset. The known position indicator,which was periodically inserted within the A area estimated by the knowndata detector and initial frequency offset estimator 9041, is inputtedto the timing error detector 1083 of the timing error recovery unit1080, to the frequency offset estimator 1092 of the carrier recoveryunit 1090, to the frequency offset estimator 1112 of the phasecompensator 1110, and to the equalizer 903.

FIG. 28 illustrates a block diagram showing the structure of one of thepartial correlators shown in FIG. 27. During the step of detecting knowndata, since a frequency offset is included in the received signal, eachpartial correlator divides the known data, which is known according toan agreement between the transmitting system and the receiving system,to K number of parts each having an L symbol length, thereby correlatingeach divided part with the corresponding part of the received signal. Inorder to do so, each partial correlator includes K number of phase andsize detector 4011 to 401K each formed in parallel, an adder 4020, and acoarse frequency offset estimator 4030.

The first phase and size detector 4011 includes an L symbol buffer4011-2, a multiplier 4011-3, an accumulator 4011-4, and a squarer4011-5. Herein, the first phase and size detector 4011 calculates thecorrelation value of the known data having a first L symbol length amongthe K number of sections. Also, the second phase and size detector 4012includes an L symbol delay 4012-1, an L symbol buffer 4012-2, amultiplier 4012-3, an accumulator 4012-4, and a squarer 4012-5. Herein,the second phase and size detector 4012 calculates the correlation valueof the known data having a second L symbol length among the K number ofsections. Finally, the N^(th) phase and size detector 401K includes a(K−1)L symbol delay 401K−1, an L symbol buffer 401K−2, a multiplier401K−3, an accumulator 401K−4, and a squarer 401K−5. Herein, the N^(th)phase and size detector 401K calculates the correlation value of theknown data having an N^(th) L symbol length among the K number ofsections.

Referring to FIG. 28, {P₀, P₁, . . . , P_(KL-1)} each being multipliedwith the received signal in the multiplier represents the known dataknown by both the transmitting system and the receiving system (i.e.,the reference known data generated from the receiving system). And, *represents a complex conjugate. For example, in the first phase and sizedetector 4011, the signal outputted from the 1/N decimator of the firstpartial correlator 3011, shown in FIG. 27, is temporarily stored in theL symbol buffer 4011-2 of the first phase and size detector 4011 andthen inputted to the multiplier 4011-3. The multiplier 4011-3 multipliesthe output of the L symbol buffer 4011-2 with the complex conjugate ofthe known data parts P₀, P₁, . . . , P_(KL-1), each having a first Lsymbol length among the known K number of sections. Then, the multipliedresult is outputted to the accumulator 4011-4. During the L symbolperiod, the accumulator 4011-4 accumulates the output of the multiplier4011-3 and, then, outputs the accumulated value to the squarer 4011-5and the coarse frequency offset estimator 4030. The output of theaccumulator 4011-4 is a correlation value having a phase and a size.Accordingly, the squarer 4011-5 calculates an absolute value of theoutput of the multiplier 4011-4 and squares the calculated absolutevalue, thereby obtaining the size of the correlation value. The obtainedsize is then inputted to the adder 4020.

The adder 4020 adds the output of the squarers corresponding to eachsize and phase detector 4011 to 401K. Then, the adder 4020 outputs theadded result to the known data place detector and frequency offsetdecider 3020. Also, the coarse frequency offset estimator 4030 receivesthe output of the accumulator corresponding to each size and phasedetector 4011 to 401K, so as to estimate the coarse frequency offset ateach corresponding sampling phase. Thereafter, the coarse frequencyoffset estimator 4030 outputs the estimated offset value to the knowndata place detector and frequency offset decider 3020. When the K numberof inputs that are outputted from the accumulator of each phase and sizedetector 4011 to 401K are each referred to as {Z₀, Z₁, . . . , Z_(K-1)},the output of the coarse frequency offset estimator 4030 may be obtainedby using Equation 4 shown below.

$\begin{matrix}{\omega_{0} = {\frac{1}{L}\arg\left\{ {\sum\limits_{n = 1}^{K - 1}\;{\left( \frac{Z_{n}}{\left| Z_{n} \right|} \right)\left( \frac{Z_{n - 1}}{\left| Z_{n - 1} \right|} \right)^{*}}} \right\}}} & {{Equation}\mspace{14mu} 4}\end{matrix}$

The known data place detector and frequency offset decider 3020 storesthe output of the partial correlator corresponding to each samplingphase during an enhanced data group cycle or a pre-decided cycle. Then,among the stored correlation values, the known data place detector andfrequency offset decider 3020 decides the place (or position)corresponding to the highest correlation value as the place forreceiving the known data. Furthermore, the known data place detector andfrequency offset decider 3020 decides the estimated value of thefrequency offset taken (or estimated) at the point of the highestcorrelation value as the coarse frequency offset value of the receivingsystem. For example, if the output of the partial correlatorcorresponding to the second partial correlator 3012 is the highestvalue, the place corresponding to the highest value is decided as theknown data place. Thereafter, the coarse frequency offset estimated bythe second partial correlator 3012 is decided as the final coarsefrequency offset, which is then outputted to the demodulator 902.Meanwhile, the DC remover 1070 removes a pilot tone signal (i.e., DCsignal), which has been inserted by the transmitting system, from thematched-filtered signal. Thereafter, the DC remover 1070 outputs theprocessed signal to the phase compensator 1110.

FIG. 29 illustrates a detailed block diagram of a DC remover accordingto an embodiment of the present invention. Herein, identical signalprocessing processes are performed on each of a real number element (orin-phase (I)) and an imaginary number element (or a quadrature (Q)) ofthe inputted complex signal, thereby estimating and removing the DCvalue of each element. In order to do so, the DC remover shown in FIG.29 includes a first DC estimator and remover 6010 and a second DCestimator and remover 6020. Herein, the first DC estimator and remover6010 includes an R sample buffer 6011, a DC estimator 6012, an M sampleholder 6013, a C sample delay 6014, and a subtractor 6015. Herein, thefirst DC estimator and remover 6010 estimates and removes the DC of thereal number element (i.e., an in-phase DC). Furthermore, the second DCestimator and remover 6020 includes an R sample buffer 6021, a DCestimator 6022, an M sample holder 6023, a C sample delay 6024, and asubtractor 6025. The second DC estimator and remover 6020 estimates andremoves the DC of the imaginary number element (i.e., a quadrature DC).In the present invention, the first DC estimator and remover 6010 andthe second DC estimator and remover 6020 may receive different inputsignals. However, each DC estimator and remover 6010 and 6020 has thesame structure. Therefore, a detailed description of the first DCestimator and remover 6010 will be presented herein, and the second DCestimator and remover 6020 will be omitted for simplicity.

More specifically, the in-phase signal matched-filtered by the matchedfilter 1060 is inputted to the R sample buffer 6011 of the first DCestimator and remover 6010 within the DC remover 1070 and is thenstored. The R sample buffer 6011 is a buffer having the length of Rsample. Herein, the output of the R sample buffer 6011 is inputted tothe DC estimator 6012 and the C sample delay 6014. The DC estimator 6012uses the data having the length of R sample, which are outputted fromthe buffer 6011, so as to estimate the DC value by using Equation 5shown below.

$\begin{matrix}{{y\lbrack n\rbrack} = {\frac{1}{R}{\sum\limits_{k = 0}^{R - 1}\;{x\left\lbrack {k + {M*n}} \right\rbrack}}}} & {{Equation}\mspace{14mu} 5}\end{matrix}$

In the above-described Equation 5, x[n] represents the inputted sampledata stored in the buffer 6011. And, y[n] indicates the DC estimationvalue. More specifically, the DC estimator 6012 accumulates R number ofsample data stored in the buffer 6011 and estimates the DC value bydividing the accumulated value by R. At this point, the stored inputsample data set is shifted as much as M sample. Herein, the DCestimation value is outputted once every M samples.

FIG. 30 illustrates a shifting of the input sample data used for DCestimation. For example, when M is equal to 1 (i.e., M=1), the DCestimator 6012 estimates the DC value each time a sample is shifted tothe buffer 6011. Accordingly, each estimated result is outputted foreach sample. If M is equal to R (i.e., M=R), the DC estimator 6012estimates the DC value each time R number of samples are shifted to thebuffer 6011. Accordingly, each estimated result is outputted for eachcycle of R samples. Therefore, in this case, the DC estimator 6012corresponds to a DC estimator that operates in a block unit of Rsamples. Herein, any value within the range of 1 and R may correspond tothe value M.

As described above, since the output of the DC estimator 6012 isoutputted after each cycle of M samples, the M sample holder 6013 holdsthe DC value estimated from the DC estimator 6012 for a period of Msamples. Then, the estimated DC value is outputted to the subtractor6015. Also, the C sample delay 6014 delays the input sample data storedin the buffer 6011 by C samples, which are then outputted to thesubtractor 6015. The subtractor 6015 subtracts the output of the Msample holder 6013 from the output of the C sample delay 6014.Thereafter, the subtractor 6015 outputs the signal having the in-phaseDC removed.

Herein, the C sample delay 6014 decides which portion of the inputsample data is to be compensated with the output of the DC estimator6012. More specifically, the DC estimator and remover 6010 may bedivided into a DC estimator 6012 for estimating the DC and thesubtractor for compensating the input sample data within the estimatedDC value. At this point, the C sample delay 6014 decides which portionof the input sample data is to be compensated with the estimated DCvalue. For example, when C is equal to 0 (i.e., C=0), the beginning ofthe R samples is compensated with the estimated DC value obtained byusing R samples. Alternatively, when C is equal to R (i.e., C=R), theend of the R samples is compensated with the estimated DC value obtainedby using R samples. Similarly, the data having the DC removed areinputted to the buffer 1111 and the frequency offset estimator 1112 ofthe phase compensator 1110.

Meanwhile, FIG. 31 illustrates a detailed block diagram of a DC removeraccording to another embodiment of the present invention. Herein,identical signal processing processes are performed on each of a realnumber element (or in-phase (I)) and an imaginary number element (or aquadrature (Q)) of the inputted complex signal, thereby estimating andremoving the DC value of each element. In order to do so, the DC removershown in FIG. 31 includes a first DC estimator and remover 8010 and asecond DC estimator and remover 8020. FIG. 31 corresponds to an infiniteimpulse response (IIR) structure.

Herein, the first DC estimator and remover 8010 includes a multiplier8011, an adder 8012, an 1 sample delay 8013, a multiplier 8014, a Csample delay 8015, and a subtractor 8016. Also, the second DC estimatorand remover 8020 includes a multiplier 8021, an adder 8022, an 1 sampledelay 8023, a multiplier 8024, a C sample delay 8025, and a subtractor8026. In the present invention, the first DC estimator and remover 8010and the second DC estimator and remover 8020 may receive different inputsignals. However, each DC estimator and remover 8010 and 8020 has thesame structure. Therefore, a detailed description of the first DCestimator and remover 8010 will be presented herein, and the second DCestimator and remover 8020 will be omitted for simplicity.

More specifically, the in-phase signal matched-filtered by the matchedfilter 1060 is inputted to the multiplier 8011 and the C sample delay8015 of the first DC estimator and remover 8010 within the DC remover1070. The multiplier 8011 multiplies a pre-determined constant α to thein-phase signal that is being inputted. Then, the multiplier 8011outputs the multiplied result to the adder 8012. The adder 8012 adds theoutput of the multiplier 8011 to the output of the multiplier 8014 thatis being fed-back. Thereafter, the adder 8012 outputs the added resultto the 1 sample delay 8013 and the subtractor 8016. More specifically,the output of the adder 8012 corresponds to the estimated in-phase DCvalue.

The 1 sample delay 8013 delays the estimated DC value by 1 sample andoutputs the DC value delayed by 1 sample to the multiplier 8014. Themultiplier 8014 multiplies a pre-determined constant (1-a) to the DCvalue delayed by 1 sample. Then, the multiplier 8014 feeds-back themultiplied result to the adder 8012. Subsequently, the C sample delay8015 delays the in-phase sample data by C samples and, then, outputs thedelayed in-phase sample data to the subtractor 8016. The subtractor 8016subtracts the output of the adder 8012 from the output of the C sampledelay 8015, thereby outputting the signal having the in-phase DC removedtherefrom. Similarly, the data having the DC removed are inputted to thebuffer 1111 and the frequency offset estimator 1112 of the phasecompensator 1110.

The frequency offset estimator 1112 uses the known sequence positionindicator outputted from the known data detector and initial frequencyoffset estimator 9041 in order to estimate the frequency offset from theknown data sequence that is being inputted, the known data sequencehaving the DC removed by the DC remover 1070. Then, the frequency offsetestimator 1112 outputs the estimated frequency offset to the holder1113. Similarly, the frequency offset estimation value is obtained ateach repetition cycle of the known data sequence.

Therefore, the holder 1113 holds the frequency offset estimation valueduring a cycle period of the known data sequence and then outputs thefrequency offset estimation value to the NCO 1114. The NCO 1114generates a complex signal corresponding to the frequency offset held bythe holder 1113 and outputs the generated complex signal to themultiplier 1115. The multiplier 1115 multiplies the complex signaloutputted from the NCO 1114 to the data being delayed by a set period oftime in the buffer 1111, thereby compensating the phase change includedin the delayed data. The data having the phase change compensated by themultiplier 1115 pass through the decimator 1500 so as to be inputted tothe equalizer 903. At this point, since the frequency offset estimatedby the frequency offset estimator 1112 of the phase compensator 1110does not pass through the loop filter, the estimated frequency offsetindicates the phase difference between the known data sequences. Inother words, the estimated frequency offset indicates a phase offset.

As described above, when the demodulator 902 performs a demodulatingprocess on the received data, the data being inputted to the equalizer903 has the data structure shown in FIG. 6A. The equalizer 903 mayperform channel equalization by using a plurality of methods. An exampleof estimating a channel impulse response (CIR) so as to perform channelequalization will be given in the description of the present invention.Most particularly, an example of estimating the CIR in accordance witheach region within the data group, which is hierarchically divided andtransmitted from the transmitting system, and applying each CIRdifferently will also be described herein. Furthermore, by using theknown data, the place and contents of which is known in accordance withan agreement between the transmitting system and the receiving system,and the field synchronization data, so as to estimate the CIR, thepresent invention may be able to perform channel equalization with morestability.

Herein, the data group that is inputted for the equalization process isdivided into regions A to C, as shown in FIG. 6A. More specifically, inthe example of the present invention, each region A, B, and C arefurther divided into regions A1 to A5, regions B1 and B2, and regions C1to C3, respectively. Referring to FIG. 6A, the CIR that is estimatedfrom the field synchronization data in the data structure is referred toas CIR_FS. Alternatively, the CIRs that are estimated from each of the 5known data sequences existing in region A are sequentially referred toas CIR_N0, CIR_N1, CIR_N2, CIR_N3, and CIR_N4.

As described above, the present invention uses the CIR estimated fromthe field synchronization data and the known data sequences in order toperform channel equalization on data within the data group. At thispoint, each of the estimated CIRs may be directly used in accordancewith the characteristics of each region within the data group.Alternatively, a plurality of the estimated CIRs may also be eitherinterpolated or extrapolated so as to create a new CIR, which is thenused for the channel equalization process.

Herein, when a value F(A) of a function F(x) at a particular point A anda value F(B) of the function F(x) at another particular point B areknown, interpolation refers to estimating a function value of a pointwithin the section between points A and B. Linear interpolationcorresponds to the simplest form among a wide range of interpolationoperations. The linear interpolation described herein is merelyexemplary among a wide range of possible interpolation methods. And,therefore, the present invention is not limited only to the examples setforth herein.

Alternatively, when a value F(A) of a function F(x) at a particularpoint A and a value F(B) of the function F(x) at another particularpoint B are known, extrapolation refers to estimating a function valueof a point outside of the section between points A and B. Linearextrapolation is the simplest form among a wide range of extrapolationoperations. Similarly, the linear extrapolation described herein ismerely exemplary among a wide range of possible extrapolation methods.And, therefore, the present invention is not limited only to theexamples set forth herein.

More specifically, in case of region C1, any one of the CIR_N4 estimatedfrom a previous data group, the CIR_FS estimated from the current datagroup that is to be processed with channel equalization, and a new CIRgenerated by extrapolating the CIR_FS of the current data group and theCIR_N0 may be used to perform channel equalization. Alternatively, incase of region B1, a variety of methods may be applied as described inthe case for region C1. For example, a new CIR created by linearlyextrapolating the CIR_FS estimated from the current data group and theCIR_N0 may be used to perform channel equalization. Also, the CIR_FSestimated from the current data group may also be used to performchannel equalization. Finally, in case of region A1, a new CIR may becreated by interpolating the CIR_FS estimated from the current datagroup and CIR_N0, which is then used to perform channel equalization.Furthermore, any one of the CIR_FS estimated from the current data groupand CIR_N0 may be used to perform channel equalization.

In case of regions A2 to A5, CIR_N(i−1) estimated from the current datagroup and CIR_N(i) may be interpolated to create a new CIR and use thenewly created CIR to perform channel equalization. Also, any one of theCIR_N(i−1) estimated from the current data group and the CIR_N(i) may beused to perform channel equalization. Alternatively, in case of regionsB2, C2, and C3, CIR_N3 and CIR_N4 both estimated from the current datagroup may be extrapolated to create a new CIR, which is then used toperform the channel equalization process. Furthermore, the CIR_N4estimated from the current data group may be used to perform the channelequalization process. Accordingly, an optimum performance may beobtained when performing channel equalization on the data inserted inthe data group. The methods of obtaining the CIRs required forperforming the channel equalization process in each region within thedata group, as described above, are merely examples given to facilitatethe understanding of the present invention. A wider range of methods mayalso be used herein. And, therefore, the present invention will not onlybe limited to the examples given in the description set forth herein.

Meanwhile, if the data being inputted to the block decoder 905 afterbeing channel equalized from the equalizer 903 correspond to the mobileservice data having additional encoding and trellis encoding performedthereon by the transmitting system, trellis decoding and additionaldecoding processes are performed on the inputted data as inverseprocesses of the transmitting system. Alternatively, if the data beinginputted to the block decoder 905 correspond to the main service datahaving only trellis encoding performed thereon, and not the additionalencoding, only the trellis decoding process is performed on the inputteddata as the inverse process of the transmitting system. The data groupdecoded by the block decoder 905 is inputted to the data deformatter906, and the main service data packet is inputted to the datadeinterleaver 909.

More specifically, if the inputted data correspond to the main servicedata, the block decoder 905 performs Viterbi decoding on the inputteddata so as to output a hard decision value or to perform a hard-decisionon a soft decision value, thereby outputting the result. Meanwhile, ifthe inputted data correspond to the mobile service data, the blockdecoder 905 outputs a hard decision value or a soft decision value withrespect to the inputted mobile service data. In other words, if theinputted data correspond to the mobile service data, the block decoder905 performs a decoding process on the data encoded by the blockprocessor and trellis encoding module of the transmitting system.

At this point, the RS frame encoder of the pre-processor included in thetransmitting system may be viewed as an external code. And, the blockprocessor and the trellis encoder may be viewed as an internal code. Inorder to maximize the performance of the external code when decodingsuch concatenated codes, the decoder of the internal code should outputa soft decision value. Therefore, the block decoder 905 may output ahard decision value on the mobile service data. However, when required,it may be more preferable for the block decoder 905 to output a softdecision value.

Meanwhile, the data deinterleaver 909, the RS decoder 910, and thederandomizer 911 are blocks required for receiving the main servicedata. Therefore, the above-mentioned blocks may not be required in thestructure of a digital broadcast receiving system that only receives themobile service data. The data deinterleaver 909 performs an inverseprocess of the data interleaver included in the transmitting system. Inother words, the data deinterleaver 909 deinterleaves the main servicedata outputted from the block decoder 905 and outputs the deinterleavedmain service data to the RS decoder 910. The RS decoder 910 performs asystematic RS decoding process on the deinterleaved data and outputs theprocessed data to the derandomizer 911. The derandomizer 911 receivesthe output of the RS decoder 910 and generates a pseudo random data byteidentical to that of the randomizer included in the digital broadcasttransmitting system. Thereafter, the derandomizer 911 performs a bitwiseexclusive OR (XOR) operation on the generated pseudo random data byte,thereby inserting the MPEG synchronization bytes to the beginning ofeach packet so as to output the data in 188-byte main service datapacket units.

Meanwhile, the data being outputted from the block decoder 905 to thedata deformatter 906 are inputted in the form of a data group. At thispoint, the data deformatter 906 already knows the structure of the datathat are to be inputted and is, therefore, capable of identifying thesignaling information, which includes the system information, and themobile service data from the data group. Thereafter, the datadeformatter 906 outputs the identified signaling information to a blockfor system information and outputs the identified mobile service data tothe RS frame decoder 907. At this point, the data deformatter 906removes the known data, trellis initialization data, and MPEG headerthat were inserted in the main service data and data group. The datadeformatter 906 also removes the RS parity that was added by the RSencoder/non-systematic RS encoder or the non-systematic RS encoder ofthe transmitting system. Thereafter, the processed data are outputted tothe RS frame decoder 907. More specifically, the RS frame decoder 907receives only the RS encoded and CRC encoded mobile service data thatare transmitted from the data deformatter 906.

The RS frame encoder 907 performs an inverse process of the RS frameencoder included in the transmitting system so as to correct the errorwithin the RS frame. Then, the RS frame decoder 907 adds the 1-byte MPEGsynchronization service data packet, which had been removed during theRS frame encoding process, to the error-corrected mobile service datapacket. Thereafter, the processed data packet is outputted to thederandomizer 908. The operation of the RS frame decoder 907 will bedescribed in detail in a later process. The derandomizer 908 performs aderandomizing process, which corresponds to the inverse process of therandomizer included in the transmitting system, on the received mobileservice data. Thereafter, the derandomized data are outputted, therebyobtaining the mobile service data transmitted from the transmittingsystem.

FIG. 32 illustrates a series of exemplary step of an error correctiondecoding process of the RS frame decoder 907 according to the presentinvention. More specifically, the RS frame decoder 907 groups mobileservice data bytes received from the data deformatter 906 so as toconfigure an RS frame. The mobile service data correspond to data RSencoded and CRC encoded from the transmitting system. FIG. 32( a)illustrates an example of configuring the RS frame. More specifically,the transmitting system divided the RS frame having the size of(N+2)*235 to 30*235 byte blocks. When it is assumed that each of thedivided mobile service data byte blocks is inserted in each data groupand then transmitted, the receiving system also groups the 30*235 mobileservice data byte blocks respectively inserted in each data group,thereby configuring an RS frame having the size of (N+2)*235. Forexample, when it is assumed that an RS frame is divided into 18 30*235byte blocks and transmitted from a burst section, the receiving systemalso groups the mobile service data bytes of 18 data groups within thecorresponding burst section, so as to configure the RS frame.Furthermore, when it is assumed that N is equal to 538 (i.e., N=538),the RS frame decoder 907 may group the mobile service data bytes withinthe 18 data groups included in a burst so as to configure a RS framehaving the size of 540*235 bytes.

Herein, when it is assumed that the block decoder 905 outputs a softdecision value for the decoding result, the RS frame decoder 907 maydecide the ‘0’ and ‘1’ of the corresponding bit by using the codes ofthe soft decision value. 8 bits that are each decided as described aboveare grouped to create 1 data byte. If the above-described process isperformed on all soft decision values of the 18 data groups included ina single burst, the RS frame having the size of 540*235 bytes may beconfigured. Additionally, the present invention uses the soft decisionvalue not only to configure the RS frame but also to configure areliability map. Herein, the reliability map indicates the reliabilityof the corresponding data byte, which is configured by grouping 8 bits,the 8 bits being decided by the codes of the soft decision value.

For example, when the absolute value of the soft decision value exceedsa pre-determined threshold value, the value of the corresponding bit,which is decided by the code of the corresponding soft decision value,is determined to be reliable. Conversely, when the absolute value of thesoft decision value does not exceed the pre-determined threshold value,the value of the corresponding bit is determined to be unreliable.Thereafter, if even a single bit among the 8 bits, which are decided bythe codes of the soft decision value and group to configure 1 data byte,is determined to be unreliable, the corresponding data byte is marked onthe reliability map as an unreliable data byte.

Herein, determining the reliability of 1 data byte is only exemplary.More specifically, when a plurality of data bytes (e.g., at least 4 databytes) are determined to be unreliable, the corresponding data bytes mayalso be marked as unreliable data bytes within the reliability map.Conversely, when all of the data bits within the 1 data byte aredetermined to be reliable (i.e., when the absolute value of the softdecision values of all 8 bits included in the 1 data byte exceed thepredetermined threshold value), the corresponding data byte is marked tobe a reliable data byte on the reliability map. Similarly, when aplurality of data bytes (e.g., at least 4 data bytes) are determined tobe reliable, the corresponding data bytes may also be marked as reliabledata bytes within the reliability map. The numbers proposed in theabove-described example are merely exemplary and, therefore, do notlimit the scope or spirit of the present invention.

The process of configuring the RS frame and the process of configuringthe reliability map both using the soft decision value may be performedat the same time. Herein, the reliability information within thereliability map is in a one-to-one correspondence with each byte withinthe RS frame. For example, if a RS frame has the size of 540*235 bytes,the reliability map is also configured to have the size of 540*235bytes. FIG. 32( a′) illustrates the process steps of configuring thereliability map according to the present invention. Meanwhile, if a RSframe is configured to have the size of (N+2)*235 bytes, the RS framedecoder 907 performs a CRC syndrome checking process on thecorresponding RS frame, thereby verifying whether any error has occurredin each row. Subsequently, as shown in FIG. 32( b), a 2-byte checksum isremoved to configure an RS frame having the size of N*235 bytes. Herein,the presence (or existence) of an error is indicated on an error flagcorresponding to each row. Similarly, since the portion of thereliability map corresponding to the CRC checksum has hardly anyapplicability, this portion is removed so that only N*235 number of thereliability information bytes remain, as shown in FIG. 32( b′).

After performing the CRC syndrome checking process, the RS frame decoder907 performs RS decoding in a column direction. Herein, a RS erasurecorrection process may be performed in accordance with the number of CRCerror flags. More specifically, as shown in FIG. 32( c), the CRC errorflag corresponding to each row within the RS frame is verified.Thereafter, the RS frame decoder 907 determines whether the number ofrows having a CRC error occurring therein is equal to or smaller thanthe maximum number of errors on which the RS erasure correction may beperformed, when performing the RS decoding process in a columndirection. The maximum number of errors corresponds to a number ofparity bytes inserted when performing the RS encoding process. In theembodiment of the present invention, it is assumed that 48 parity byteshave been added to each column.

If the number of rows having the CRC errors occurring therein is smallerthan or equal to the maximum number of errors (i.e., 48 errors accordingto this embodiment) that can be corrected by the RS erasure decodingprocess, a (235,187)-RS erasure decoding process is performed in acolumn direction on the RS frame having 235 N-byte rows, as shown inFIG. 32( d). Thereafter, as shown in FIG. 32( f), the 48-byte paritydata that have been added at the end of each column are removed.Conversely, however, if the number of rows having the CRC errorsoccurring therein is greater than the maximum number of errors (i.e., 48errors) that can be corrected by the RS erasure decoding process, the RSerasure decoding process cannot be performed. In this case, the errormay be corrected by performing a general RS decoding process. Inaddition, the reliability map, which has been created based upon thesoft decision value along with the RS frame, may be used to furtherenhance the error correction ability (or performance) of the presentinvention.

More specifically, the RS frame decoder 907 compares the absolute valueof the soft decision value of the block decoder 905 with thepre-determined threshold value, so as to determine the reliability ofthe bit value decided by the code of the corresponding soft decisionvalue. Also, 8 bits, each being determined by the code of the softdecision value, are grouped to form 1 data byte. Accordingly, thereliability information on this 1 data byte is indicated on thereliability map. Therefore, as shown in FIG. 32( e), even though aparticular row is determined to have an error occurring therein basedupon a CRC syndrome checking process on the particular row, the presentinvention does not assume that all bytes included in the row have errorsoccurring therein. The present invention refers to the reliabilityinformation of the reliability map and sets only the bytes that havebeen determined to be unreliable as erroneous bytes. In other words,with disregard to whether or not a CRC error exists within thecorresponding row, only the bytes that are determined to be unreliablebased upon the reliability map are set as erasure points.

According to another method, when it is determined that CRC errors areincluded in the corresponding row, based upon the result of the CRCsyndrome checking result, only the bytes that are determined by thereliability map to be unreliable are set as errors. More specifically,only the bytes corresponding to the row that is determined to haveerrors included therein and being determined to be unreliable based uponthe reliability information, are set as the erasure points. Thereafter,if the number of error points for each column is smaller than or equalto the maximum number of errors (i.e., 48 errors) that can be correctedby the RS erasure decoding process, an RS erasure decoding process isperformed on the corresponding column. Conversely, if the number oferror points for each column is greater than the maximum number oferrors (i.e., 48 errors) that can be corrected by the RS erasuredecoding process, a general decoding process is performed on thecorresponding column.

More specifically, if the number of rows having CRC errors includedtherein is greater than the maximum number of errors (i.e., 48 errors)that can be corrected by the RS erasure decoding process, either an RSerasure decoding process or a general RS decoding process is performedon a column that is decided based upon the reliability information ofthe reliability map, in accordance with the number of erasure pointswithin the corresponding column. For example, it is assumed that thenumber of rows having CRC errors included therein within the RS frame isgreater than 48. And, it is also assumed that the number of erasurepoints decided based upon the reliability information of the reliabilitymap is indicated as 40 erasure points in the first column and as 50erasure points in the second column. In this case, a (235,187)-RSerasure decoding process is performed on the first column.Alternatively, a (235,187)-RS decoding process is performed on thesecond column. When error correction decoding is performed on all columndirections within the RS frame by using the above-described process, the48-byte parity data which were added at the end of each column areremoved, as shown in FIG. 32( f).

As described above, even though the total number of CRC errorscorresponding to each row within the RS frame is greater than themaximum number of errors that can be corrected by the RS erasuredecoding process, when the number of bytes determined to have a lowreliability level, based upon the reliability information on thereliability map within a particular column, while performing errorcorrection decoding on the particular column. Herein, the differencebetween the general RS decoding process and the RS erasure decodingprocess is the number of errors that can be corrected. Morespecifically, when performing the general RS decoding process, thenumber of errors corresponding to half of the number of parity bytes(i.e., (number of parity bytes)/2) that are inserted during the RSencoding process may be error corrected (e.g., 24 errors may becorrected). Alternatively, when performing the RS erasure decodingprocess, the number of errors corresponding to the number of paritybytes that are inserted during the RS encoding process may be errorcorrected (e.g., 48 errors may be corrected).

After performing the error correction decoding process, as describedabove, a RS frame configured of 187 N-byte rows (or packets) maybeobtained, as shown in FIG. 32( f). Furthermore, the RS frame having thesize of N*187 bytes is sequentially outputted in N number of 187-byteunits. Herein, as shown in FIG. 32( g), the 1-byte MPEG synchronizationbyte that was removed by the transmitting system is added at the end ofeach 187-byte packet, thereby outputting 188-byte mobile service datapackets.

As described above, the digital broadcasting system and the dataprocessing method according to the present invention have the followingadvantages. More specifically, the digital broadcasting receiving systemand method according to the present invention is highly protectedagainst (or resistant to) any error that may occur when transmittingmobile service data through a channel. And, the present invention isalso highly compatible to the conventional receiving system. Moreover,the present invention may also receive the mobile service data withoutany error even in channels having severe ghost effect and noise.

Additionally, by inserting known data in a particular position (orplace) within a data region and transmitting the processed data, thereceiving performance of the receiving system may be enhanced even in achannel environment that is liable to frequent changes. Also, bymultiplexing mobile service data with main service data into a burststructure, the power consumption of the receiving system may be reduced.Further, by having the transmitting system periodically ornon-periodically transmit known data having a pattern pre-decided inaccordance with an agreement between the transmitting system and thereceiving system, and by having the receiving system use the known datafor performing carrier recovery and timing recovery, and forcompensating a phase change between repeating known data sequences, thereceiving performance of the receiving system may be enhanced in asituation undergoing severe and frequent channel changes. Finally, thepresent invention is even more effective when applied to mobile andportable receivers, which are also liable to a frequent change inchannel and which require protection (or resistance) against intensenoise.

It will be apparent to those skilled in the art that variousmodifications and variations can be made in the present inventionwithout departing from the spirit or scope of the inventions. Thus, itis intended that the present invention covers the modifications andvariations of this invention provided they come within the scope of theappended claims and their equivalents.

What is claimed is:
 1. A method for processing digital broadcast data ina digital broadcast transmitter, the method comprising: randomizingmobile service data; performing Cyclic Redundancy Check (CRC) encodingon the randomized mobile service data; performing encoding on theCRC-encoded mobile service data at a first code rate; performingencoding on transmission parameters at a second code rate; blockinterleaving the mobile service data encoded at the first code rate; andconvolutional interleaving the block-interleaved mobile service data. 2.The method of claim 1, further comprising: forming data groups includingthe mobile service data encoded at the first code rate, wherein each ofthe data groups comprises a first region and a second region, whereinthe first region comprises: an Nth segment comprising K mobile servicedata bytes, an (N+1)th segment comprising L mobile service data bytes,and an (N+2)th segment comprising M mobile service data bytes, whereinthe second region comprises: an Oth segment comprising X mobile servicedata bytes, an (O+1)th segment comprising Y mobile service data bytes,and an (O+2)th segment comprising Z mobile service data bytes, whereinthe variables K, L, M, N, O, X, Y, and Z are integers greater than 0,and wherein K<L<M, X=Y=Z, and N<O.
 3. The method of claim 1, furthercomprising: performing Reed-Solomon (RS) encoding on the randomizedmobile service data to build an RS frame, wherein the RS framecomprises: an RS frame payload including the randomized mobile servicedata; RS parity data added at bottom ends of columns of the RS framepayload; and CRC data added at right ends of rows of the RS framepayload.
 4. The method of claim 3, wherein the transmission parametersinclude information for indicating a number of bytes of the RS paritydata per RS frame column.
 5. The method of claim 1, wherein thetransmission parameters include information to identify a size of CRCdata when the CRC-encoding is performed.
 6. The method of claim 1,further comprising: multiplexing mobile service data packets and mainservice data packets, wherein the mobile service data packets includethe mobile service data and the main service data packets include mainservice data.
 7. The method of claim 6, further comprising: randomizingall data in the main service data packets of the multiplexed datapackets; and performing RS encoding on the main service data packets inwhich all data are randomized.
 8. A digital broadcast transmitter forprocessing digital broadcast data, the digital broadcast transmittercomprising: a first randomizer to randomize mobile service data; a firstencoder to perform Cyclic Redundancy Check (CRC) encoding on therandomized mobile service data; a second encoder to perform encoding onthe CRC-encoded mobile service data at a first code rate and to performencoding on transmission parameters at a second code rate; a firstinterleaver to block interleave the mobile service data encoded at thefirst code rate; and a second interleaver to convolutional interleavethe block-interleaved mobile service data.
 9. The digital broadcasttransmitter of claim 8, further comprising: a group formatter to formdata groups including the mobile service data encoded at the first coderate, wherein each of the data groups comprises a first region and asecond region, wherein the first region comprises: an Nth segmentcomprising K mobile service data bytes, an (N+1)th segment comprising Lmobile service data bytes, and an (N+2)th segment comprising M mobileservice data bytes, wherein the second region comprises: an Oth segmentcomprising X mobile service data bytes, an (0+1)th segment comprising Ymobile service data bytes, and an (0+2)th segment comprising Z mobileservice data bytes, wherein the variables K, L, M, N, O, X, Y, and Z areintegers greater than 0, and wherein K<L<M, X=Y=Z, and N<O.
 10. Thedigital broadcast transmitter of claim 8, wherein the first encoderfurther performs Reed-Solomon (RS) encoding on the randomized mobileservice data to build an RS frame, and wherein the RS frame comprises:an RS frame payload including the randomized mobile service data; RSparity data added at bottom ends of columns of the RS frame payload; andCRC data added at right ends of rows of the RS frame payload.
 11. Thedigital broadcast transmitter of claim 10, wherein the transmissionparameters include information for indicating a number of bytes of theRS parity data per RS frame column.
 12. The digital broadcasttransmitter of claim 8, wherein the transmission parameters includeinformation to identify a size of CRC data when the CRC-encoding isperformed.
 13. The digital broadcast transmitter of claim 8, furthercomprising: a multiplexer to multiplex mobile service data packets andmain service data packets, wherein the mobile service data packetsinclude the mobile service data and the main service data packetsinclude main service data.
 14. The digital broadcast transmitter ofclaim 13, further comprising: a second randomizer to randomize all datain the main service data packets of the multiplexed data packets; and athird encoder to perform RS encoding on the main service data packets inwhich all data are randomized.